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Traktor/myenv/Lib/site-packages/scipy/signal/_ltisys.py

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losowanie zdjec
2024-05-26 05:12:46 +02:00
"""
ltisys -- a collection of classes and functions for modeling linear
time invariant systems.
"""
#
# Author: Travis Oliphant 2001
#
# Feb 2010: Warren Weckesser
# Rewrote lsim2 and added impulse2.
# Apr 2011: Jeffrey Armstrong <jeff@approximatrix.com>
# Added dlsim, dstep, dimpulse, cont2discrete
# Aug 2013: Juan Luis Cano
# Rewrote abcd_normalize.
# Jan 2015: Irvin Probst irvin DOT probst AT ensta-bretagne DOT fr
# Added pole placement
# Mar 2015: Clancy Rowley
# Rewrote lsim
# May 2015: Felix Berkenkamp
# Split lti class into subclasses
# Merged discrete systems and added dlti
import warnings
# np.linalg.qr fails on some tests with LinAlgError: zgeqrf returns -7
# use scipy's qr until this is solved
from scipy.linalg import qr as s_qr
from scipy import linalg
from scipy.interpolate import make_interp_spline
from ._filter_design import (tf2zpk, zpk2tf, normalize, freqs, freqz, freqs_zpk,
freqz_zpk)
from ._lti_conversion import (tf2ss, abcd_normalize, ss2tf, zpk2ss, ss2zpk,
cont2discrete, _atleast_2d_or_none)
import numpy
import numpy as np
from numpy import (real, atleast_1d, squeeze, asarray, zeros,
dot, transpose, ones, linspace)
import copy
__all__ = ['lti', 'dlti', 'TransferFunction', 'ZerosPolesGain', 'StateSpace',
'lsim', 'impulse', 'step', 'bode',
'freqresp', 'place_poles', 'dlsim', 'dstep', 'dimpulse',
'dfreqresp', 'dbode']
class LinearTimeInvariant:
def __new__(cls, *system, **kwargs):
"""Create a new object, don't allow direct instances."""
if cls is LinearTimeInvariant:
raise NotImplementedError('The LinearTimeInvariant class is not '
'meant to be used directly, use `lti` '
'or `dlti` instead.')
return super().__new__(cls)
def __init__(self):
"""
Initialize the `lti` baseclass.
The heavy lifting is done by the subclasses.
"""
super().__init__()
self.inputs = None
self.outputs = None
self._dt = None
@property
def dt(self):
"""Return the sampling time of the system, `None` for `lti` systems."""
return self._dt
@property
def _dt_dict(self):
if self.dt is None:
return {}
else:
return {'dt': self.dt}
@property
def zeros(self):
"""Zeros of the system."""
return self.to_zpk().zeros
@property
def poles(self):
"""Poles of the system."""
return self.to_zpk().poles
def _as_ss(self):
"""Convert to `StateSpace` system, without copying.
Returns
-------
sys: StateSpace
The `StateSpace` system. If the class is already an instance of
`StateSpace` then this instance is returned.
"""
if isinstance(self, StateSpace):
return self
else:
return self.to_ss()
def _as_zpk(self):
"""Convert to `ZerosPolesGain` system, without copying.
Returns
-------
sys: ZerosPolesGain
The `ZerosPolesGain` system. If the class is already an instance of
`ZerosPolesGain` then this instance is returned.
"""
if isinstance(self, ZerosPolesGain):
return self
else:
return self.to_zpk()
def _as_tf(self):
"""Convert to `TransferFunction` system, without copying.
Returns
-------
sys: ZerosPolesGain
The `TransferFunction` system. If the class is already an instance of
`TransferFunction` then this instance is returned.
"""
if isinstance(self, TransferFunction):
return self
else:
return self.to_tf()
class lti(LinearTimeInvariant):
r"""
Continuous-time linear time invariant system base class.
Parameters
----------
*system : arguments
The `lti` class can be instantiated with either 2, 3 or 4 arguments.
The following gives the number of arguments and the corresponding
continuous-time subclass that is created:
* 2: `TransferFunction`: (numerator, denominator)
* 3: `ZerosPolesGain`: (zeros, poles, gain)
* 4: `StateSpace`: (A, B, C, D)
Each argument can be an array or a sequence.
See Also
--------
ZerosPolesGain, StateSpace, TransferFunction, dlti
Notes
-----
`lti` instances do not exist directly. Instead, `lti` creates an instance
of one of its subclasses: `StateSpace`, `TransferFunction` or
`ZerosPolesGain`.
If (numerator, denominator) is passed in for ``*system``, coefficients for
both the numerator and denominator should be specified in descending
exponent order (e.g., ``s^2 + 3s + 5`` would be represented as ``[1, 3,
5]``).
Changing the value of properties that are not directly part of the current
system representation (such as the `zeros` of a `StateSpace` system) is
very inefficient and may lead to numerical inaccuracies. It is better to
convert to the specific system representation first. For example, call
``sys = sys.to_zpk()`` before accessing/changing the zeros, poles or gain.
Examples
--------
>>> from scipy import signal
>>> signal.lti(1, 2, 3, 4)
StateSpaceContinuous(
array([[1]]),
array([[2]]),
array([[3]]),
array([[4]]),
dt: None
)
Construct the transfer function
:math:`H(s) = \frac{5(s - 1)(s - 2)}{(s - 3)(s - 4)}`:
>>> signal.lti([1, 2], [3, 4], 5)
ZerosPolesGainContinuous(
array([1, 2]),
array([3, 4]),
5,
dt: None
)
Construct the transfer function :math:`H(s) = \frac{3s + 4}{1s + 2}`:
>>> signal.lti([3, 4], [1, 2])
TransferFunctionContinuous(
array([3., 4.]),
array([1., 2.]),
dt: None
)
"""
def __new__(cls, *system):
"""Create an instance of the appropriate subclass."""
if cls is lti:
N = len(system)
if N == 2:
return TransferFunctionContinuous.__new__(
TransferFunctionContinuous, *system)
elif N == 3:
return ZerosPolesGainContinuous.__new__(
ZerosPolesGainContinuous, *system)
elif N == 4:
return StateSpaceContinuous.__new__(StateSpaceContinuous,
*system)
else:
raise ValueError("`system` needs to be an instance of `lti` "
"or have 2, 3 or 4 arguments.")
# __new__ was called from a subclass, let it call its own functions
return super().__new__(cls)
def __init__(self, *system):
"""
Initialize the `lti` baseclass.
The heavy lifting is done by the subclasses.
"""
super().__init__(*system)
def impulse(self, X0=None, T=None, N=None):
"""
Return the impulse response of a continuous-time system.
See `impulse` for details.
"""
return impulse(self, X0=X0, T=T, N=N)
def step(self, X0=None, T=None, N=None):
"""
Return the step response of a continuous-time system.
See `step` for details.
"""
return step(self, X0=X0, T=T, N=N)
def output(self, U, T, X0=None):
"""
Return the response of a continuous-time system to input `U`.
See `lsim` for details.
"""
return lsim(self, U, T, X0=X0)
def bode(self, w=None, n=100):
"""
Calculate Bode magnitude and phase data of a continuous-time system.
Returns a 3-tuple containing arrays of frequencies [rad/s], magnitude
[dB] and phase [deg]. See `bode` for details.
Examples
--------
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
>>> sys = signal.TransferFunction([1], [1, 1])
>>> w, mag, phase = sys.bode()
>>> plt.figure()
>>> plt.semilogx(w, mag) # Bode magnitude plot
>>> plt.figure()
>>> plt.semilogx(w, phase) # Bode phase plot
>>> plt.show()
"""
return bode(self, w=w, n=n)
def freqresp(self, w=None, n=10000):
"""
Calculate the frequency response of a continuous-time system.
Returns a 2-tuple containing arrays of frequencies [rad/s] and
complex magnitude.
See `freqresp` for details.
"""
return freqresp(self, w=w, n=n)
def to_discrete(self, dt, method='zoh', alpha=None):
"""Return a discretized version of the current system.
Parameters: See `cont2discrete` for details.
Returns
-------
sys: instance of `dlti`
"""
raise NotImplementedError('to_discrete is not implemented for this '
'system class.')
class dlti(LinearTimeInvariant):
r"""
Discrete-time linear time invariant system base class.
Parameters
----------
*system: arguments
The `dlti` class can be instantiated with either 2, 3 or 4 arguments.
The following gives the number of arguments and the corresponding
discrete-time subclass that is created:
* 2: `TransferFunction`: (numerator, denominator)
* 3: `ZerosPolesGain`: (zeros, poles, gain)
* 4: `StateSpace`: (A, B, C, D)
Each argument can be an array or a sequence.
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to ``True``
(unspecified sampling time). Must be specified as a keyword argument,
for example, ``dt=0.1``.
See Also
--------
ZerosPolesGain, StateSpace, TransferFunction, lti
Notes
-----
`dlti` instances do not exist directly. Instead, `dlti` creates an instance
of one of its subclasses: `StateSpace`, `TransferFunction` or
`ZerosPolesGain`.
Changing the value of properties that are not directly part of the current
system representation (such as the `zeros` of a `StateSpace` system) is
very inefficient and may lead to numerical inaccuracies. It is better to
convert to the specific system representation first. For example, call
``sys = sys.to_zpk()`` before accessing/changing the zeros, poles or gain.
If (numerator, denominator) is passed in for ``*system``, coefficients for
both the numerator and denominator should be specified in descending
exponent order (e.g., ``z^2 + 3z + 5`` would be represented as ``[1, 3,
5]``).
.. versionadded:: 0.18.0
Examples
--------
>>> from scipy import signal
>>> signal.dlti(1, 2, 3, 4)
StateSpaceDiscrete(
array([[1]]),
array([[2]]),
array([[3]]),
array([[4]]),
dt: True
)
>>> signal.dlti(1, 2, 3, 4, dt=0.1)
StateSpaceDiscrete(
array([[1]]),
array([[2]]),
array([[3]]),
array([[4]]),
dt: 0.1
)
Construct the transfer function
:math:`H(z) = \frac{5(z - 1)(z - 2)}{(z - 3)(z - 4)}` with a sampling time
of 0.1 seconds:
>>> signal.dlti([1, 2], [3, 4], 5, dt=0.1)
ZerosPolesGainDiscrete(
array([1, 2]),
array([3, 4]),
5,
dt: 0.1
)
Construct the transfer function :math:`H(z) = \frac{3z + 4}{1z + 2}` with
a sampling time of 0.1 seconds:
>>> signal.dlti([3, 4], [1, 2], dt=0.1)
TransferFunctionDiscrete(
array([3., 4.]),
array([1., 2.]),
dt: 0.1
)
"""
def __new__(cls, *system, **kwargs):
"""Create an instance of the appropriate subclass."""
if cls is dlti:
N = len(system)
if N == 2:
return TransferFunctionDiscrete.__new__(
TransferFunctionDiscrete, *system, **kwargs)
elif N == 3:
return ZerosPolesGainDiscrete.__new__(ZerosPolesGainDiscrete,
*system, **kwargs)
elif N == 4:
return StateSpaceDiscrete.__new__(StateSpaceDiscrete, *system,
**kwargs)
else:
raise ValueError("`system` needs to be an instance of `dlti` "
"or have 2, 3 or 4 arguments.")
# __new__ was called from a subclass, let it call its own functions
return super().__new__(cls)
def __init__(self, *system, **kwargs):
"""
Initialize the `lti` baseclass.
The heavy lifting is done by the subclasses.
"""
dt = kwargs.pop('dt', True)
super().__init__(*system, **kwargs)
self.dt = dt
@property
def dt(self):
"""Return the sampling time of the system."""
return self._dt
@dt.setter
def dt(self, dt):
self._dt = dt
def impulse(self, x0=None, t=None, n=None):
"""
Return the impulse response of the discrete-time `dlti` system.
See `dimpulse` for details.
"""
return dimpulse(self, x0=x0, t=t, n=n)
def step(self, x0=None, t=None, n=None):
"""
Return the step response of the discrete-time `dlti` system.
See `dstep` for details.
"""
return dstep(self, x0=x0, t=t, n=n)
def output(self, u, t, x0=None):
"""
Return the response of the discrete-time system to input `u`.
See `dlsim` for details.
"""
return dlsim(self, u, t, x0=x0)
def bode(self, w=None, n=100):
r"""
Calculate Bode magnitude and phase data of a discrete-time system.
Returns a 3-tuple containing arrays of frequencies [rad/s], magnitude
[dB] and phase [deg]. See `dbode` for details.
Examples
--------
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
Construct the transfer function :math:`H(z) = \frac{1}{z^2 + 2z + 3}`
with sampling time 0.5s:
>>> sys = signal.TransferFunction([1], [1, 2, 3], dt=0.5)
Equivalent: signal.dbode(sys)
>>> w, mag, phase = sys.bode()
>>> plt.figure()
>>> plt.semilogx(w, mag) # Bode magnitude plot
>>> plt.figure()
>>> plt.semilogx(w, phase) # Bode phase plot
>>> plt.show()
"""
return dbode(self, w=w, n=n)
def freqresp(self, w=None, n=10000, whole=False):
"""
Calculate the frequency response of a discrete-time system.
Returns a 2-tuple containing arrays of frequencies [rad/s] and
complex magnitude.
See `dfreqresp` for details.
"""
return dfreqresp(self, w=w, n=n, whole=whole)
class TransferFunction(LinearTimeInvariant):
r"""Linear Time Invariant system class in transfer function form.
Represents the system as the continuous-time transfer function
:math:`H(s)=\sum_{i=0}^N b[N-i] s^i / \sum_{j=0}^M a[M-j] s^j` or the
discrete-time transfer function
:math:`H(z)=\sum_{i=0}^N b[N-i] z^i / \sum_{j=0}^M a[M-j] z^j`, where
:math:`b` are elements of the numerator `num`, :math:`a` are elements of
the denominator `den`, and ``N == len(b) - 1``, ``M == len(a) - 1``.
`TransferFunction` systems inherit additional
functionality from the `lti`, respectively the `dlti` classes, depending on
which system representation is used.
Parameters
----------
*system: arguments
The `TransferFunction` class can be instantiated with 1 or 2
arguments. The following gives the number of input arguments and their
interpretation:
* 1: `lti` or `dlti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 2: array_like: (numerator, denominator)
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to `None`
(continuous-time). Must be specified as a keyword argument, for
example, ``dt=0.1``.
See Also
--------
ZerosPolesGain, StateSpace, lti, dlti
tf2ss, tf2zpk, tf2sos
Notes
-----
Changing the value of properties that are not part of the
`TransferFunction` system representation (such as the `A`, `B`, `C`, `D`
state-space matrices) is very inefficient and may lead to numerical
inaccuracies. It is better to convert to the specific system
representation first. For example, call ``sys = sys.to_ss()`` before
accessing/changing the A, B, C, D system matrices.
If (numerator, denominator) is passed in for ``*system``, coefficients
for both the numerator and denominator should be specified in descending
exponent order (e.g. ``s^2 + 3s + 5`` or ``z^2 + 3z + 5`` would be
represented as ``[1, 3, 5]``)
Examples
--------
Construct the transfer function
:math:`H(s) = \frac{s^2 + 3s + 3}{s^2 + 2s + 1}`:
>>> from scipy import signal
>>> num = [1, 3, 3]
>>> den = [1, 2, 1]
>>> signal.TransferFunction(num, den)
TransferFunctionContinuous(
array([1., 3., 3.]),
array([1., 2., 1.]),
dt: None
)
Construct the transfer function
:math:`H(z) = \frac{z^2 + 3z + 3}{z^2 + 2z + 1}` with a sampling time of
0.1 seconds:
>>> signal.TransferFunction(num, den, dt=0.1)
TransferFunctionDiscrete(
array([1., 3., 3.]),
array([1., 2., 1.]),
dt: 0.1
)
"""
def __new__(cls, *system, **kwargs):
"""Handle object conversion if input is an instance of lti."""
if len(system) == 1 and isinstance(system[0], LinearTimeInvariant):
return system[0].to_tf()
# Choose whether to inherit from `lti` or from `dlti`
if cls is TransferFunction:
if kwargs.get('dt') is None:
return TransferFunctionContinuous.__new__(
TransferFunctionContinuous,
*system,
**kwargs)
else:
return TransferFunctionDiscrete.__new__(
TransferFunctionDiscrete,
*system,
**kwargs)
# No special conversion needed
return super().__new__(cls)
def __init__(self, *system, **kwargs):
"""Initialize the state space LTI system."""
# Conversion of lti instances is handled in __new__
if isinstance(system[0], LinearTimeInvariant):
return
# Remove system arguments, not needed by parents anymore
super().__init__(**kwargs)
self._num = None
self._den = None
self.num, self.den = normalize(*system)
def __repr__(self):
"""Return representation of the system's transfer function"""
return '{}(\n{},\n{},\ndt: {}\n)'.format(
self.__class__.__name__,
repr(self.num),
repr(self.den),
repr(self.dt),
)
@property
def num(self):
"""Numerator of the `TransferFunction` system."""
return self._num
@num.setter
def num(self, num):
self._num = atleast_1d(num)
# Update dimensions
if len(self.num.shape) > 1:
self.outputs, self.inputs = self.num.shape
else:
self.outputs = 1
self.inputs = 1
@property
def den(self):
"""Denominator of the `TransferFunction` system."""
return self._den
@den.setter
def den(self, den):
self._den = atleast_1d(den)
def _copy(self, system):
"""
Copy the parameters of another `TransferFunction` object
Parameters
----------
system : `TransferFunction`
The `StateSpace` system that is to be copied
"""
self.num = system.num
self.den = system.den
def to_tf(self):
"""
Return a copy of the current `TransferFunction` system.
Returns
-------
sys : instance of `TransferFunction`
The current system (copy)
"""
return copy.deepcopy(self)
def to_zpk(self):
"""
Convert system representation to `ZerosPolesGain`.
Returns
-------
sys : instance of `ZerosPolesGain`
Zeros, poles, gain representation of the current system
"""
return ZerosPolesGain(*tf2zpk(self.num, self.den),
**self._dt_dict)
def to_ss(self):
"""
Convert system representation to `StateSpace`.
Returns
-------
sys : instance of `StateSpace`
State space model of the current system
"""
return StateSpace(*tf2ss(self.num, self.den),
**self._dt_dict)
@staticmethod
def _z_to_zinv(num, den):
"""Change a transfer function from the variable `z` to `z**-1`.
Parameters
----------
num, den: 1d array_like
Sequences representing the coefficients of the numerator and
denominator polynomials, in order of descending degree of 'z'.
That is, ``5z**2 + 3z + 2`` is presented as ``[5, 3, 2]``.
Returns
-------
num, den: 1d array_like
Sequences representing the coefficients of the numerator and
denominator polynomials, in order of ascending degree of 'z**-1'.
That is, ``5 + 3 z**-1 + 2 z**-2`` is presented as ``[5, 3, 2]``.
"""
diff = len(num) - len(den)
if diff > 0:
den = np.hstack((np.zeros(diff), den))
elif diff < 0:
num = np.hstack((np.zeros(-diff), num))
return num, den
@staticmethod
def _zinv_to_z(num, den):
"""Change a transfer function from the variable `z` to `z**-1`.
Parameters
----------
num, den: 1d array_like
Sequences representing the coefficients of the numerator and
denominator polynomials, in order of ascending degree of 'z**-1'.
That is, ``5 + 3 z**-1 + 2 z**-2`` is presented as ``[5, 3, 2]``.
Returns
-------
num, den: 1d array_like
Sequences representing the coefficients of the numerator and
denominator polynomials, in order of descending degree of 'z'.
That is, ``5z**2 + 3z + 2`` is presented as ``[5, 3, 2]``.
"""
diff = len(num) - len(den)
if diff > 0:
den = np.hstack((den, np.zeros(diff)))
elif diff < 0:
num = np.hstack((num, np.zeros(-diff)))
return num, den
class TransferFunctionContinuous(TransferFunction, lti):
r"""
Continuous-time Linear Time Invariant system in transfer function form.
Represents the system as the transfer function
:math:`H(s)=\sum_{i=0}^N b[N-i] s^i / \sum_{j=0}^M a[M-j] s^j`, where
:math:`b` are elements of the numerator `num`, :math:`a` are elements of
the denominator `den`, and ``N == len(b) - 1``, ``M == len(a) - 1``.
Continuous-time `TransferFunction` systems inherit additional
functionality from the `lti` class.
Parameters
----------
*system: arguments
The `TransferFunction` class can be instantiated with 1 or 2
arguments. The following gives the number of input arguments and their
interpretation:
* 1: `lti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 2: array_like: (numerator, denominator)
See Also
--------
ZerosPolesGain, StateSpace, lti
tf2ss, tf2zpk, tf2sos
Notes
-----
Changing the value of properties that are not part of the
`TransferFunction` system representation (such as the `A`, `B`, `C`, `D`
state-space matrices) is very inefficient and may lead to numerical
inaccuracies. It is better to convert to the specific system
representation first. For example, call ``sys = sys.to_ss()`` before
accessing/changing the A, B, C, D system matrices.
If (numerator, denominator) is passed in for ``*system``, coefficients
for both the numerator and denominator should be specified in descending
exponent order (e.g. ``s^2 + 3s + 5`` would be represented as
``[1, 3, 5]``)
Examples
--------
Construct the transfer function
:math:`H(s) = \frac{s^2 + 3s + 3}{s^2 + 2s + 1}`:
>>> from scipy import signal
>>> num = [1, 3, 3]
>>> den = [1, 2, 1]
>>> signal.TransferFunction(num, den)
TransferFunctionContinuous(
array([ 1., 3., 3.]),
array([ 1., 2., 1.]),
dt: None
)
"""
def to_discrete(self, dt, method='zoh', alpha=None):
"""
Returns the discretized `TransferFunction` system.
Parameters: See `cont2discrete` for details.
Returns
-------
sys: instance of `dlti` and `StateSpace`
"""
return TransferFunction(*cont2discrete((self.num, self.den),
dt,
method=method,
alpha=alpha)[:-1],
dt=dt)
class TransferFunctionDiscrete(TransferFunction, dlti):
r"""
Discrete-time Linear Time Invariant system in transfer function form.
Represents the system as the transfer function
:math:`H(z)=\sum_{i=0}^N b[N-i] z^i / \sum_{j=0}^M a[M-j] z^j`, where
:math:`b` are elements of the numerator `num`, :math:`a` are elements of
the denominator `den`, and ``N == len(b) - 1``, ``M == len(a) - 1``.
Discrete-time `TransferFunction` systems inherit additional functionality
from the `dlti` class.
Parameters
----------
*system: arguments
The `TransferFunction` class can be instantiated with 1 or 2
arguments. The following gives the number of input arguments and their
interpretation:
* 1: `dlti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 2: array_like: (numerator, denominator)
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to `True`
(unspecified sampling time). Must be specified as a keyword argument,
for example, ``dt=0.1``.
See Also
--------
ZerosPolesGain, StateSpace, dlti
tf2ss, tf2zpk, tf2sos
Notes
-----
Changing the value of properties that are not part of the
`TransferFunction` system representation (such as the `A`, `B`, `C`, `D`
state-space matrices) is very inefficient and may lead to numerical
inaccuracies.
If (numerator, denominator) is passed in for ``*system``, coefficients
for both the numerator and denominator should be specified in descending
exponent order (e.g., ``z^2 + 3z + 5`` would be represented as
``[1, 3, 5]``).
Examples
--------
Construct the transfer function
:math:`H(z) = \frac{z^2 + 3z + 3}{z^2 + 2z + 1}` with a sampling time of
0.5 seconds:
>>> from scipy import signal
>>> num = [1, 3, 3]
>>> den = [1, 2, 1]
>>> signal.TransferFunction(num, den, dt=0.5)
TransferFunctionDiscrete(
array([ 1., 3., 3.]),
array([ 1., 2., 1.]),
dt: 0.5
)
"""
pass
class ZerosPolesGain(LinearTimeInvariant):
r"""
Linear Time Invariant system class in zeros, poles, gain form.
Represents the system as the continuous- or discrete-time transfer function
:math:`H(s)=k \prod_i (s - z[i]) / \prod_j (s - p[j])`, where :math:`k` is
the `gain`, :math:`z` are the `zeros` and :math:`p` are the `poles`.
`ZerosPolesGain` systems inherit additional functionality from the `lti`,
respectively the `dlti` classes, depending on which system representation
is used.
Parameters
----------
*system : arguments
The `ZerosPolesGain` class can be instantiated with 1 or 3
arguments. The following gives the number of input arguments and their
interpretation:
* 1: `lti` or `dlti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 3: array_like: (zeros, poles, gain)
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to `None`
(continuous-time). Must be specified as a keyword argument, for
example, ``dt=0.1``.
See Also
--------
TransferFunction, StateSpace, lti, dlti
zpk2ss, zpk2tf, zpk2sos
Notes
-----
Changing the value of properties that are not part of the
`ZerosPolesGain` system representation (such as the `A`, `B`, `C`, `D`
state-space matrices) is very inefficient and may lead to numerical
inaccuracies. It is better to convert to the specific system
representation first. For example, call ``sys = sys.to_ss()`` before
accessing/changing the A, B, C, D system matrices.
Examples
--------
Construct the transfer function
:math:`H(s) = \frac{5(s - 1)(s - 2)}{(s - 3)(s - 4)}`:
>>> from scipy import signal
>>> signal.ZerosPolesGain([1, 2], [3, 4], 5)
ZerosPolesGainContinuous(
array([1, 2]),
array([3, 4]),
5,
dt: None
)
Construct the transfer function
:math:`H(z) = \frac{5(z - 1)(z - 2)}{(z - 3)(z - 4)}` with a sampling time
of 0.1 seconds:
>>> signal.ZerosPolesGain([1, 2], [3, 4], 5, dt=0.1)
ZerosPolesGainDiscrete(
array([1, 2]),
array([3, 4]),
5,
dt: 0.1
)
"""
def __new__(cls, *system, **kwargs):
"""Handle object conversion if input is an instance of `lti`"""
if len(system) == 1 and isinstance(system[0], LinearTimeInvariant):
return system[0].to_zpk()
# Choose whether to inherit from `lti` or from `dlti`
if cls is ZerosPolesGain:
if kwargs.get('dt') is None:
return ZerosPolesGainContinuous.__new__(
ZerosPolesGainContinuous,
*system,
**kwargs)
else:
return ZerosPolesGainDiscrete.__new__(
ZerosPolesGainDiscrete,
*system,
**kwargs
)
# No special conversion needed
return super().__new__(cls)
def __init__(self, *system, **kwargs):
"""Initialize the zeros, poles, gain system."""
# Conversion of lti instances is handled in __new__
if isinstance(system[0], LinearTimeInvariant):
return
super().__init__(**kwargs)
self._zeros = None
self._poles = None
self._gain = None
self.zeros, self.poles, self.gain = system
def __repr__(self):
"""Return representation of the `ZerosPolesGain` system."""
return '{}(\n{},\n{},\n{},\ndt: {}\n)'.format(
self.__class__.__name__,
repr(self.zeros),
repr(self.poles),
repr(self.gain),
repr(self.dt),
)
@property
def zeros(self):
"""Zeros of the `ZerosPolesGain` system."""
return self._zeros
@zeros.setter
def zeros(self, zeros):
self._zeros = atleast_1d(zeros)
# Update dimensions
if len(self.zeros.shape) > 1:
self.outputs, self.inputs = self.zeros.shape
else:
self.outputs = 1
self.inputs = 1
@property
def poles(self):
"""Poles of the `ZerosPolesGain` system."""
return self._poles
@poles.setter
def poles(self, poles):
self._poles = atleast_1d(poles)
@property
def gain(self):
"""Gain of the `ZerosPolesGain` system."""
return self._gain
@gain.setter
def gain(self, gain):
self._gain = gain
def _copy(self, system):
"""
Copy the parameters of another `ZerosPolesGain` system.
Parameters
----------
system : instance of `ZerosPolesGain`
The zeros, poles gain system that is to be copied
"""
self.poles = system.poles
self.zeros = system.zeros
self.gain = system.gain
def to_tf(self):
"""
Convert system representation to `TransferFunction`.
Returns
-------
sys : instance of `TransferFunction`
Transfer function of the current system
"""
return TransferFunction(*zpk2tf(self.zeros, self.poles, self.gain),
**self._dt_dict)
def to_zpk(self):
"""
Return a copy of the current 'ZerosPolesGain' system.
Returns
-------
sys : instance of `ZerosPolesGain`
The current system (copy)
"""
return copy.deepcopy(self)
def to_ss(self):
"""
Convert system representation to `StateSpace`.
Returns
-------
sys : instance of `StateSpace`
State space model of the current system
"""
return StateSpace(*zpk2ss(self.zeros, self.poles, self.gain),
**self._dt_dict)
class ZerosPolesGainContinuous(ZerosPolesGain, lti):
r"""
Continuous-time Linear Time Invariant system in zeros, poles, gain form.
Represents the system as the continuous time transfer function
:math:`H(s)=k \prod_i (s - z[i]) / \prod_j (s - p[j])`, where :math:`k` is
the `gain`, :math:`z` are the `zeros` and :math:`p` are the `poles`.
Continuous-time `ZerosPolesGain` systems inherit additional functionality
from the `lti` class.
Parameters
----------
*system : arguments
The `ZerosPolesGain` class can be instantiated with 1 or 3
arguments. The following gives the number of input arguments and their
interpretation:
* 1: `lti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 3: array_like: (zeros, poles, gain)
See Also
--------
TransferFunction, StateSpace, lti
zpk2ss, zpk2tf, zpk2sos
Notes
-----
Changing the value of properties that are not part of the
`ZerosPolesGain` system representation (such as the `A`, `B`, `C`, `D`
state-space matrices) is very inefficient and may lead to numerical
inaccuracies. It is better to convert to the specific system
representation first. For example, call ``sys = sys.to_ss()`` before
accessing/changing the A, B, C, D system matrices.
Examples
--------
Construct the transfer function
:math:`H(s)=\frac{5(s - 1)(s - 2)}{(s - 3)(s - 4)}`:
>>> from scipy import signal
>>> signal.ZerosPolesGain([1, 2], [3, 4], 5)
ZerosPolesGainContinuous(
array([1, 2]),
array([3, 4]),
5,
dt: None
)
"""
def to_discrete(self, dt, method='zoh', alpha=None):
"""
Returns the discretized `ZerosPolesGain` system.
Parameters: See `cont2discrete` for details.
Returns
-------
sys: instance of `dlti` and `ZerosPolesGain`
"""
return ZerosPolesGain(
*cont2discrete((self.zeros, self.poles, self.gain),
dt,
method=method,
alpha=alpha)[:-1],
dt=dt)
class ZerosPolesGainDiscrete(ZerosPolesGain, dlti):
r"""
Discrete-time Linear Time Invariant system in zeros, poles, gain form.
Represents the system as the discrete-time transfer function
:math:`H(z)=k \prod_i (z - q[i]) / \prod_j (z - p[j])`, where :math:`k` is
the `gain`, :math:`q` are the `zeros` and :math:`p` are the `poles`.
Discrete-time `ZerosPolesGain` systems inherit additional functionality
from the `dlti` class.
Parameters
----------
*system : arguments
The `ZerosPolesGain` class can be instantiated with 1 or 3
arguments. The following gives the number of input arguments and their
interpretation:
* 1: `dlti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 3: array_like: (zeros, poles, gain)
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to `True`
(unspecified sampling time). Must be specified as a keyword argument,
for example, ``dt=0.1``.
See Also
--------
TransferFunction, StateSpace, dlti
zpk2ss, zpk2tf, zpk2sos
Notes
-----
Changing the value of properties that are not part of the
`ZerosPolesGain` system representation (such as the `A`, `B`, `C`, `D`
state-space matrices) is very inefficient and may lead to numerical
inaccuracies. It is better to convert to the specific system
representation first. For example, call ``sys = sys.to_ss()`` before
accessing/changing the A, B, C, D system matrices.
Examples
--------
Construct the transfer function
:math:`H(s) = \frac{5(s - 1)(s - 2)}{(s - 3)(s - 4)}`:
>>> from scipy import signal
>>> signal.ZerosPolesGain([1, 2], [3, 4], 5)
ZerosPolesGainContinuous(
array([1, 2]),
array([3, 4]),
5,
dt: None
)
Construct the transfer function
:math:`H(z) = \frac{5(z - 1)(z - 2)}{(z - 3)(z - 4)}` with a sampling time
of 0.1 seconds:
>>> signal.ZerosPolesGain([1, 2], [3, 4], 5, dt=0.1)
ZerosPolesGainDiscrete(
array([1, 2]),
array([3, 4]),
5,
dt: 0.1
)
"""
pass
class StateSpace(LinearTimeInvariant):
r"""
Linear Time Invariant system in state-space form.
Represents the system as the continuous-time, first order differential
equation :math:`\dot{x} = A x + B u` or the discrete-time difference
equation :math:`x[k+1] = A x[k] + B u[k]`. `StateSpace` systems
inherit additional functionality from the `lti`, respectively the `dlti`
classes, depending on which system representation is used.
Parameters
----------
*system: arguments
The `StateSpace` class can be instantiated with 1 or 4 arguments.
The following gives the number of input arguments and their
interpretation:
* 1: `lti` or `dlti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 4: array_like: (A, B, C, D)
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to `None`
(continuous-time). Must be specified as a keyword argument, for
example, ``dt=0.1``.
See Also
--------
TransferFunction, ZerosPolesGain, lti, dlti
ss2zpk, ss2tf, zpk2sos
Notes
-----
Changing the value of properties that are not part of the
`StateSpace` system representation (such as `zeros` or `poles`) is very
inefficient and may lead to numerical inaccuracies. It is better to
convert to the specific system representation first. For example, call
``sys = sys.to_zpk()`` before accessing/changing the zeros, poles or gain.
Examples
--------
>>> from scipy import signal
>>> import numpy as np
>>> a = np.array([[0, 1], [0, 0]])
>>> b = np.array([[0], [1]])
>>> c = np.array([[1, 0]])
>>> d = np.array([[0]])
>>> sys = signal.StateSpace(a, b, c, d)
>>> print(sys)
StateSpaceContinuous(
array([[0, 1],
[0, 0]]),
array([[0],
[1]]),
array([[1, 0]]),
array([[0]]),
dt: None
)
>>> sys.to_discrete(0.1)
StateSpaceDiscrete(
array([[1. , 0.1],
[0. , 1. ]]),
array([[0.005],
[0.1 ]]),
array([[1, 0]]),
array([[0]]),
dt: 0.1
)
>>> a = np.array([[1, 0.1], [0, 1]])
>>> b = np.array([[0.005], [0.1]])
>>> signal.StateSpace(a, b, c, d, dt=0.1)
StateSpaceDiscrete(
array([[1. , 0.1],
[0. , 1. ]]),
array([[0.005],
[0.1 ]]),
array([[1, 0]]),
array([[0]]),
dt: 0.1
)
"""
# Override NumPy binary operations and ufuncs
__array_priority__ = 100.0
__array_ufunc__ = None
def __new__(cls, *system, **kwargs):
"""Create new StateSpace object and settle inheritance."""
# Handle object conversion if input is an instance of `lti`
if len(system) == 1 and isinstance(system[0], LinearTimeInvariant):
return system[0].to_ss()
# Choose whether to inherit from `lti` or from `dlti`
if cls is StateSpace:
if kwargs.get('dt') is None:
return StateSpaceContinuous.__new__(StateSpaceContinuous,
*system, **kwargs)
else:
return StateSpaceDiscrete.__new__(StateSpaceDiscrete,
*system, **kwargs)
# No special conversion needed
return super().__new__(cls)
def __init__(self, *system, **kwargs):
"""Initialize the state space lti/dlti system."""
# Conversion of lti instances is handled in __new__
if isinstance(system[0], LinearTimeInvariant):
return
# Remove system arguments, not needed by parents anymore
super().__init__(**kwargs)
self._A = None
self._B = None
self._C = None
self._D = None
self.A, self.B, self.C, self.D = abcd_normalize(*system)
def __repr__(self):
"""Return representation of the `StateSpace` system."""
return '{}(\n{},\n{},\n{},\n{},\ndt: {}\n)'.format(
self.__class__.__name__,
repr(self.A),
repr(self.B),
repr(self.C),
repr(self.D),
repr(self.dt),
)
def _check_binop_other(self, other):
return isinstance(other, (StateSpace, np.ndarray, float, complex,
np.number, int))
def __mul__(self, other):
"""
Post-multiply another system or a scalar
Handles multiplication of systems in the sense of a frequency domain
multiplication. That means, given two systems E1(s) and E2(s), their
multiplication, H(s) = E1(s) * E2(s), means that applying H(s) to U(s)
is equivalent to first applying E2(s), and then E1(s).
Notes
-----
For SISO systems the order of system application does not matter.
However, for MIMO systems, where the two systems are matrices, the
order above ensures standard Matrix multiplication rules apply.
"""
if not self._check_binop_other(other):
return NotImplemented
if isinstance(other, StateSpace):
# Disallow mix of discrete and continuous systems.
if type(other) is not type(self):
return NotImplemented
if self.dt != other.dt:
raise TypeError('Cannot multiply systems with different `dt`.')
n1 = self.A.shape[0]
n2 = other.A.shape[0]
# Interconnection of systems
# x1' = A1 x1 + B1 u1
# y1 = C1 x1 + D1 u1
# x2' = A2 x2 + B2 y1
# y2 = C2 x2 + D2 y1
#
# Plugging in with u1 = y2 yields
# [x1'] [A1 B1*C2 ] [x1] [B1*D2]
# [x2'] = [0 A2 ] [x2] + [B2 ] u2
# [x1]
# y2 = [C1 D1*C2] [x2] + D1*D2 u2
a = np.vstack((np.hstack((self.A, np.dot(self.B, other.C))),
np.hstack((zeros((n2, n1)), other.A))))
b = np.vstack((np.dot(self.B, other.D), other.B))
c = np.hstack((self.C, np.dot(self.D, other.C)))
d = np.dot(self.D, other.D)
else:
# Assume that other is a scalar / matrix
# For post multiplication the input gets scaled
a = self.A
b = np.dot(self.B, other)
c = self.C
d = np.dot(self.D, other)
common_dtype = np.result_type(a.dtype, b.dtype, c.dtype, d.dtype)
return StateSpace(np.asarray(a, dtype=common_dtype),
np.asarray(b, dtype=common_dtype),
np.asarray(c, dtype=common_dtype),
np.asarray(d, dtype=common_dtype),
**self._dt_dict)
def __rmul__(self, other):
"""Pre-multiply a scalar or matrix (but not StateSpace)"""
if not self._check_binop_other(other) or isinstance(other, StateSpace):
return NotImplemented
# For pre-multiplication only the output gets scaled
a = self.A
b = self.B
c = np.dot(other, self.C)
d = np.dot(other, self.D)
common_dtype = np.result_type(a.dtype, b.dtype, c.dtype, d.dtype)
return StateSpace(np.asarray(a, dtype=common_dtype),
np.asarray(b, dtype=common_dtype),
np.asarray(c, dtype=common_dtype),
np.asarray(d, dtype=common_dtype),
**self._dt_dict)
def __neg__(self):
"""Negate the system (equivalent to pre-multiplying by -1)."""
return StateSpace(self.A, self.B, -self.C, -self.D, **self._dt_dict)
def __add__(self, other):
"""
Adds two systems in the sense of frequency domain addition.
"""
if not self._check_binop_other(other):
return NotImplemented
if isinstance(other, StateSpace):
# Disallow mix of discrete and continuous systems.
if type(other) is not type(self):
raise TypeError(f'Cannot add {type(self)} and {type(other)}')
if self.dt != other.dt:
raise TypeError('Cannot add systems with different `dt`.')
# Interconnection of systems
# x1' = A1 x1 + B1 u
# y1 = C1 x1 + D1 u
# x2' = A2 x2 + B2 u
# y2 = C2 x2 + D2 u
# y = y1 + y2
#
# Plugging in yields
# [x1'] [A1 0 ] [x1] [B1]
# [x2'] = [0 A2] [x2] + [B2] u
# [x1]
# y = [C1 C2] [x2] + [D1 + D2] u
a = linalg.block_diag(self.A, other.A)
b = np.vstack((self.B, other.B))
c = np.hstack((self.C, other.C))
d = self.D + other.D
else:
other = np.atleast_2d(other)
if self.D.shape == other.shape:
# A scalar/matrix is really just a static system (A=0, B=0, C=0)
a = self.A
b = self.B
c = self.C
d = self.D + other
else:
raise ValueError("Cannot add systems with incompatible "
f"dimensions ({self.D.shape} and {other.shape})")
common_dtype = np.result_type(a.dtype, b.dtype, c.dtype, d.dtype)
return StateSpace(np.asarray(a, dtype=common_dtype),
np.asarray(b, dtype=common_dtype),
np.asarray(c, dtype=common_dtype),
np.asarray(d, dtype=common_dtype),
**self._dt_dict)
def __sub__(self, other):
if not self._check_binop_other(other):
return NotImplemented
return self.__add__(-other)
def __radd__(self, other):
if not self._check_binop_other(other):
return NotImplemented
return self.__add__(other)
def __rsub__(self, other):
if not self._check_binop_other(other):
return NotImplemented
return (-self).__add__(other)
def __truediv__(self, other):
"""
Divide by a scalar
"""
# Division by non-StateSpace scalars
if not self._check_binop_other(other) or isinstance(other, StateSpace):
return NotImplemented
if isinstance(other, np.ndarray) and other.ndim > 0:
# It's ambiguous what this means, so disallow it
raise ValueError("Cannot divide StateSpace by non-scalar numpy arrays")
return self.__mul__(1/other)
@property
def A(self):
"""State matrix of the `StateSpace` system."""
return self._A
@A.setter
def A(self, A):
self._A = _atleast_2d_or_none(A)
@property
def B(self):
"""Input matrix of the `StateSpace` system."""
return self._B
@B.setter
def B(self, B):
self._B = _atleast_2d_or_none(B)
self.inputs = self.B.shape[-1]
@property
def C(self):
"""Output matrix of the `StateSpace` system."""
return self._C
@C.setter
def C(self, C):
self._C = _atleast_2d_or_none(C)
self.outputs = self.C.shape[0]
@property
def D(self):
"""Feedthrough matrix of the `StateSpace` system."""
return self._D
@D.setter
def D(self, D):
self._D = _atleast_2d_or_none(D)
def _copy(self, system):
"""
Copy the parameters of another `StateSpace` system.
Parameters
----------
system : instance of `StateSpace`
The state-space system that is to be copied
"""
self.A = system.A
self.B = system.B
self.C = system.C
self.D = system.D
def to_tf(self, **kwargs):
"""
Convert system representation to `TransferFunction`.
Parameters
----------
kwargs : dict, optional
Additional keywords passed to `ss2zpk`
Returns
-------
sys : instance of `TransferFunction`
Transfer function of the current system
"""
return TransferFunction(*ss2tf(self._A, self._B, self._C, self._D,
**kwargs), **self._dt_dict)
def to_zpk(self, **kwargs):
"""
Convert system representation to `ZerosPolesGain`.
Parameters
----------
kwargs : dict, optional
Additional keywords passed to `ss2zpk`
Returns
-------
sys : instance of `ZerosPolesGain`
Zeros, poles, gain representation of the current system
"""
return ZerosPolesGain(*ss2zpk(self._A, self._B, self._C, self._D,
**kwargs), **self._dt_dict)
def to_ss(self):
"""
Return a copy of the current `StateSpace` system.
Returns
-------
sys : instance of `StateSpace`
The current system (copy)
"""
return copy.deepcopy(self)
class StateSpaceContinuous(StateSpace, lti):
r"""
Continuous-time Linear Time Invariant system in state-space form.
Represents the system as the continuous-time, first order differential
equation :math:`\dot{x} = A x + B u`.
Continuous-time `StateSpace` systems inherit additional functionality
from the `lti` class.
Parameters
----------
*system: arguments
The `StateSpace` class can be instantiated with 1 or 3 arguments.
The following gives the number of input arguments and their
interpretation:
* 1: `lti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 4: array_like: (A, B, C, D)
See Also
--------
TransferFunction, ZerosPolesGain, lti
ss2zpk, ss2tf, zpk2sos
Notes
-----
Changing the value of properties that are not part of the
`StateSpace` system representation (such as `zeros` or `poles`) is very
inefficient and may lead to numerical inaccuracies. It is better to
convert to the specific system representation first. For example, call
``sys = sys.to_zpk()`` before accessing/changing the zeros, poles or gain.
Examples
--------
>>> import numpy as np
>>> from scipy import signal
>>> a = np.array([[0, 1], [0, 0]])
>>> b = np.array([[0], [1]])
>>> c = np.array([[1, 0]])
>>> d = np.array([[0]])
>>> sys = signal.StateSpace(a, b, c, d)
>>> print(sys)
StateSpaceContinuous(
array([[0, 1],
[0, 0]]),
array([[0],
[1]]),
array([[1, 0]]),
array([[0]]),
dt: None
)
"""
def to_discrete(self, dt, method='zoh', alpha=None):
"""
Returns the discretized `StateSpace` system.
Parameters: See `cont2discrete` for details.
Returns
-------
sys: instance of `dlti` and `StateSpace`
"""
return StateSpace(*cont2discrete((self.A, self.B, self.C, self.D),
dt,
method=method,
alpha=alpha)[:-1],
dt=dt)
class StateSpaceDiscrete(StateSpace, dlti):
r"""
Discrete-time Linear Time Invariant system in state-space form.
Represents the system as the discrete-time difference equation
:math:`x[k+1] = A x[k] + B u[k]`.
`StateSpace` systems inherit additional functionality from the `dlti`
class.
Parameters
----------
*system: arguments
The `StateSpace` class can be instantiated with 1 or 3 arguments.
The following gives the number of input arguments and their
interpretation:
* 1: `dlti` system: (`StateSpace`, `TransferFunction` or
`ZerosPolesGain`)
* 4: array_like: (A, B, C, D)
dt: float, optional
Sampling time [s] of the discrete-time systems. Defaults to `True`
(unspecified sampling time). Must be specified as a keyword argument,
for example, ``dt=0.1``.
See Also
--------
TransferFunction, ZerosPolesGain, dlti
ss2zpk, ss2tf, zpk2sos
Notes
-----
Changing the value of properties that are not part of the
`StateSpace` system representation (such as `zeros` or `poles`) is very
inefficient and may lead to numerical inaccuracies. It is better to
convert to the specific system representation first. For example, call
``sys = sys.to_zpk()`` before accessing/changing the zeros, poles or gain.
Examples
--------
>>> import numpy as np
>>> from scipy import signal
>>> a = np.array([[1, 0.1], [0, 1]])
>>> b = np.array([[0.005], [0.1]])
>>> c = np.array([[1, 0]])
>>> d = np.array([[0]])
>>> signal.StateSpace(a, b, c, d, dt=0.1)
StateSpaceDiscrete(
array([[ 1. , 0.1],
[ 0. , 1. ]]),
array([[ 0.005],
[ 0.1 ]]),
array([[1, 0]]),
array([[0]]),
dt: 0.1
)
"""
pass
def lsim(system, U, T, X0=None, interp=True):
"""
Simulate output of a continuous-time linear system.
Parameters
----------
system : an instance of the LTI class or a tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1: (instance of `lti`)
* 2: (num, den)
* 3: (zeros, poles, gain)
* 4: (A, B, C, D)
U : array_like
An input array describing the input at each time `T`
(interpolation is assumed between given times). If there are
multiple inputs, then each column of the rank-2 array
represents an input. If U = 0 or None, a zero input is used.
T : array_like
The time steps at which the input is defined and at which the
output is desired. Must be nonnegative, increasing, and equally spaced.
X0 : array_like, optional
The initial conditions on the state vector (zero by default).
interp : bool, optional
Whether to use linear (True, the default) or zero-order-hold (False)
interpolation for the input array.
Returns
-------
T : 1D ndarray
Time values for the output.
yout : 1D ndarray
System response.
xout : ndarray
Time evolution of the state vector.
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``s^2 + 3s + 5`` would be represented as ``[1, 3, 5]``).
Examples
--------
We'll use `lsim` to simulate an analog Bessel filter applied to
a signal.
>>> import numpy as np
>>> from scipy.signal import bessel, lsim
>>> import matplotlib.pyplot as plt
Create a low-pass Bessel filter with a cutoff of 12 Hz.
>>> b, a = bessel(N=5, Wn=2*np.pi*12, btype='lowpass', analog=True)
Generate data to which the filter is applied.
>>> t = np.linspace(0, 1.25, 500, endpoint=False)
The input signal is the sum of three sinusoidal curves, with
frequencies 4 Hz, 40 Hz, and 80 Hz. The filter should mostly
eliminate the 40 Hz and 80 Hz components, leaving just the 4 Hz signal.
>>> u = (np.cos(2*np.pi*4*t) + 0.6*np.sin(2*np.pi*40*t) +
... 0.5*np.cos(2*np.pi*80*t))
Simulate the filter with `lsim`.
>>> tout, yout, xout = lsim((b, a), U=u, T=t)
Plot the result.
>>> plt.plot(t, u, 'r', alpha=0.5, linewidth=1, label='input')
>>> plt.plot(tout, yout, 'k', linewidth=1.5, label='output')
>>> plt.legend(loc='best', shadow=True, framealpha=1)
>>> plt.grid(alpha=0.3)
>>> plt.xlabel('t')
>>> plt.show()
In a second example, we simulate a double integrator ``y'' = u``, with
a constant input ``u = 1``. We'll use the state space representation
of the integrator.
>>> from scipy.signal import lti
>>> A = np.array([[0.0, 1.0], [0.0, 0.0]])
>>> B = np.array([[0.0], [1.0]])
>>> C = np.array([[1.0, 0.0]])
>>> D = 0.0
>>> system = lti(A, B, C, D)
`t` and `u` define the time and input signal for the system to
be simulated.
>>> t = np.linspace(0, 5, num=50)
>>> u = np.ones_like(t)
Compute the simulation, and then plot `y`. As expected, the plot shows
the curve ``y = 0.5*t**2``.
>>> tout, y, x = lsim(system, u, t)
>>> plt.plot(t, y)
>>> plt.grid(alpha=0.3)
>>> plt.xlabel('t')
>>> plt.show()
"""
if isinstance(system, lti):
sys = system._as_ss()
elif isinstance(system, dlti):
raise AttributeError('lsim can only be used with continuous-time '
'systems.')
else:
sys = lti(*system)._as_ss()
T = atleast_1d(T)
if len(T.shape) != 1:
raise ValueError("T must be a rank-1 array.")
A, B, C, D = map(np.asarray, (sys.A, sys.B, sys.C, sys.D))
n_states = A.shape[0]
n_inputs = B.shape[1]
n_steps = T.size
if X0 is None:
X0 = zeros(n_states, sys.A.dtype)
xout = np.empty((n_steps, n_states), sys.A.dtype)
if T[0] == 0:
xout[0] = X0
elif T[0] > 0:
# step forward to initial time, with zero input
xout[0] = dot(X0, linalg.expm(transpose(A) * T[0]))
else:
raise ValueError("Initial time must be nonnegative")
no_input = (U is None or
(isinstance(U, (int, float)) and U == 0.) or
not np.any(U))
if n_steps == 1:
yout = squeeze(xout @ C.T)
if not no_input:
yout += squeeze(U @ D.T)
return T, yout, squeeze(xout)
dt = T[1] - T[0]
if not np.allclose(np.diff(T), dt):
raise ValueError("Time steps are not equally spaced.")
if no_input:
# Zero input: just use matrix exponential
# take transpose because state is a row vector
expAT_dt = linalg.expm(A.T * dt)
for i in range(1, n_steps):
xout[i] = xout[i-1] @ expAT_dt
yout = squeeze(xout @ C.T)
return T, yout, squeeze(xout)
# Nonzero input
U = atleast_1d(U)
if U.ndim == 1:
U = U[:, np.newaxis]
if U.shape[0] != n_steps:
raise ValueError("U must have the same number of rows "
"as elements in T.")
if U.shape[1] != n_inputs:
raise ValueError("System does not define that many inputs.")
if not interp:
# Zero-order hold
# Algorithm: to integrate from time 0 to time dt, we solve
# xdot = A x + B u, x(0) = x0
# udot = 0, u(0) = u0.
#
# Solution is
# [ x(dt) ] [ A*dt B*dt ] [ x0 ]
# [ u(dt) ] = exp [ 0 0 ] [ u0 ]
M = np.vstack([np.hstack([A * dt, B * dt]),
np.zeros((n_inputs, n_states + n_inputs))])
# transpose everything because the state and input are row vectors
expMT = linalg.expm(M.T)
Ad = expMT[:n_states, :n_states]
Bd = expMT[n_states:, :n_states]
for i in range(1, n_steps):
xout[i] = xout[i-1] @ Ad + U[i-1] @ Bd
else:
# Linear interpolation between steps
# Algorithm: to integrate from time 0 to time dt, with linear
# interpolation between inputs u(0) = u0 and u(dt) = u1, we solve
# xdot = A x + B u, x(0) = x0
# udot = (u1 - u0) / dt, u(0) = u0.
#
# Solution is
# [ x(dt) ] [ A*dt B*dt 0 ] [ x0 ]
# [ u(dt) ] = exp [ 0 0 I ] [ u0 ]
# [u1 - u0] [ 0 0 0 ] [u1 - u0]
M = np.vstack([np.hstack([A * dt, B * dt,
np.zeros((n_states, n_inputs))]),
np.hstack([np.zeros((n_inputs, n_states + n_inputs)),
np.identity(n_inputs)]),
np.zeros((n_inputs, n_states + 2 * n_inputs))])
expMT = linalg.expm(M.T)
Ad = expMT[:n_states, :n_states]
Bd1 = expMT[n_states+n_inputs:, :n_states]
Bd0 = expMT[n_states:n_states + n_inputs, :n_states] - Bd1
for i in range(1, n_steps):
xout[i] = xout[i-1] @ Ad + U[i-1] @ Bd0 + U[i] @ Bd1
yout = squeeze(xout @ C.T) + squeeze(U @ D.T)
return T, yout, squeeze(xout)
def _default_response_times(A, n):
"""Compute a reasonable set of time samples for the response time.
This function is used by `impulse` and `step` to compute the response time
when the `T` argument to the function is None.
Parameters
----------
A : array_like
The system matrix, which is square.
n : int
The number of time samples to generate.
Returns
-------
t : ndarray
The 1-D array of length `n` of time samples at which the response
is to be computed.
"""
# Create a reasonable time interval.
# TODO: This could use some more work.
# For example, what is expected when the system is unstable?
vals = linalg.eigvals(A)
r = min(abs(real(vals)))
if r == 0.0:
r = 1.0
tc = 1.0 / r
t = linspace(0.0, 7 * tc, n)
return t
def impulse(system, X0=None, T=None, N=None):
"""Impulse response of continuous-time system.
Parameters
----------
system : an instance of the LTI class or a tuple of array_like
describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1 (instance of `lti`)
* 2 (num, den)
* 3 (zeros, poles, gain)
* 4 (A, B, C, D)
X0 : array_like, optional
Initial state-vector. Defaults to zero.
T : array_like, optional
Time points. Computed if not given.
N : int, optional
The number of time points to compute (if `T` is not given).
Returns
-------
T : ndarray
A 1-D array of time points.
yout : ndarray
A 1-D array containing the impulse response of the system (except for
singularities at zero).
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``s^2 + 3s + 5`` would be represented as ``[1, 3, 5]``).
Examples
--------
Compute the impulse response of a second order system with a repeated
root: ``x''(t) + 2*x'(t) + x(t) = u(t)``
>>> from scipy import signal
>>> system = ([1.0], [1.0, 2.0, 1.0])
>>> t, y = signal.impulse(system)
>>> import matplotlib.pyplot as plt
>>> plt.plot(t, y)
"""
if isinstance(system, lti):
sys = system._as_ss()
elif isinstance(system, dlti):
raise AttributeError('impulse can only be used with continuous-time '
'systems.')
else:
sys = lti(*system)._as_ss()
if X0 is None:
X = squeeze(sys.B)
else:
X = squeeze(sys.B + X0)
if N is None:
N = 100
if T is None:
T = _default_response_times(sys.A, N)
else:
T = asarray(T)
_, h, _ = lsim(sys, 0., T, X, interp=False)
return T, h
def step(system, X0=None, T=None, N=None):
"""Step response of continuous-time system.
Parameters
----------
system : an instance of the LTI class or a tuple of array_like
describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1 (instance of `lti`)
* 2 (num, den)
* 3 (zeros, poles, gain)
* 4 (A, B, C, D)
X0 : array_like, optional
Initial state-vector (default is zero).
T : array_like, optional
Time points (computed if not given).
N : int, optional
Number of time points to compute if `T` is not given.
Returns
-------
T : 1D ndarray
Output time points.
yout : 1D ndarray
Step response of system.
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``s^2 + 3s + 5`` would be represented as ``[1, 3, 5]``).
Examples
--------
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
>>> lti = signal.lti([1.0], [1.0, 1.0])
>>> t, y = signal.step(lti)
>>> plt.plot(t, y)
>>> plt.xlabel('Time [s]')
>>> plt.ylabel('Amplitude')
>>> plt.title('Step response for 1. Order Lowpass')
>>> plt.grid()
"""
if isinstance(system, lti):
sys = system._as_ss()
elif isinstance(system, dlti):
raise AttributeError('step can only be used with continuous-time '
'systems.')
else:
sys = lti(*system)._as_ss()
if N is None:
N = 100
if T is None:
T = _default_response_times(sys.A, N)
else:
T = asarray(T)
U = ones(T.shape, sys.A.dtype)
vals = lsim(sys, U, T, X0=X0, interp=False)
return vals[0], vals[1]
def bode(system, w=None, n=100):
"""
Calculate Bode magnitude and phase data of a continuous-time system.
Parameters
----------
system : an instance of the LTI class or a tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1 (instance of `lti`)
* 2 (num, den)
* 3 (zeros, poles, gain)
* 4 (A, B, C, D)
w : array_like, optional
Array of frequencies (in rad/s). Magnitude and phase data is calculated
for every value in this array. If not given a reasonable set will be
calculated.
n : int, optional
Number of frequency points to compute if `w` is not given. The `n`
frequencies are logarithmically spaced in an interval chosen to
include the influence of the poles and zeros of the system.
Returns
-------
w : 1D ndarray
Frequency array [rad/s]
mag : 1D ndarray
Magnitude array [dB]
phase : 1D ndarray
Phase array [deg]
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``s^2 + 3s + 5`` would be represented as ``[1, 3, 5]``).
.. versionadded:: 0.11.0
Examples
--------
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
>>> sys = signal.TransferFunction([1], [1, 1])
>>> w, mag, phase = signal.bode(sys)
>>> plt.figure()
>>> plt.semilogx(w, mag) # Bode magnitude plot
>>> plt.figure()
>>> plt.semilogx(w, phase) # Bode phase plot
>>> plt.show()
"""
w, y = freqresp(system, w=w, n=n)
mag = 20.0 * numpy.log10(abs(y))
phase = numpy.unwrap(numpy.arctan2(y.imag, y.real)) * 180.0 / numpy.pi
return w, mag, phase
def freqresp(system, w=None, n=10000):
r"""Calculate the frequency response of a continuous-time system.
Parameters
----------
system : an instance of the `lti` class or a tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1 (instance of `lti`)
* 2 (num, den)
* 3 (zeros, poles, gain)
* 4 (A, B, C, D)
w : array_like, optional
Array of frequencies (in rad/s). Magnitude and phase data is
calculated for every value in this array. If not given, a reasonable
set will be calculated.
n : int, optional
Number of frequency points to compute if `w` is not given. The `n`
frequencies are logarithmically spaced in an interval chosen to
include the influence of the poles and zeros of the system.
Returns
-------
w : 1D ndarray
Frequency array [rad/s]
H : 1D ndarray
Array of complex magnitude values
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``s^2 + 3s + 5`` would be represented as ``[1, 3, 5]``).
Examples
--------
Generating the Nyquist plot of a transfer function
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
Construct the transfer function :math:`H(s) = \frac{5}{(s-1)^3}`:
>>> s1 = signal.ZerosPolesGain([], [1, 1, 1], [5])
>>> w, H = signal.freqresp(s1)
>>> plt.figure()
>>> plt.plot(H.real, H.imag, "b")
>>> plt.plot(H.real, -H.imag, "r")
>>> plt.show()
"""
if isinstance(system, lti):
if isinstance(system, (TransferFunction, ZerosPolesGain)):
sys = system
else:
sys = system._as_zpk()
elif isinstance(system, dlti):
raise AttributeError('freqresp can only be used with continuous-time '
'systems.')
else:
sys = lti(*system)._as_zpk()
if sys.inputs != 1 or sys.outputs != 1:
raise ValueError("freqresp() requires a SISO (single input, single "
"output) system.")
if w is not None:
worN = w
else:
worN = n
if isinstance(sys, TransferFunction):
# In the call to freqs(), sys.num.ravel() is used because there are
# cases where sys.num is a 2-D array with a single row.
w, h = freqs(sys.num.ravel(), sys.den, worN=worN)
elif isinstance(sys, ZerosPolesGain):
w, h = freqs_zpk(sys.zeros, sys.poles, sys.gain, worN=worN)
return w, h
# This class will be used by place_poles to return its results
# see https://code.activestate.com/recipes/52308/
class Bunch:
def __init__(self, **kwds):
self.__dict__.update(kwds)
def _valid_inputs(A, B, poles, method, rtol, maxiter):
"""
Check the poles come in complex conjugage pairs
Check shapes of A, B and poles are compatible.
Check the method chosen is compatible with provided poles
Return update method to use and ordered poles
"""
poles = np.asarray(poles)
if poles.ndim > 1:
raise ValueError("Poles must be a 1D array like.")
# Will raise ValueError if poles do not come in complex conjugates pairs
poles = _order_complex_poles(poles)
if A.ndim > 2:
raise ValueError("A must be a 2D array/matrix.")
if B.ndim > 2:
raise ValueError("B must be a 2D array/matrix")
if A.shape[0] != A.shape[1]:
raise ValueError("A must be square")
if len(poles) > A.shape[0]:
raise ValueError("maximum number of poles is %d but you asked for %d" %
(A.shape[0], len(poles)))
if len(poles) < A.shape[0]:
raise ValueError("number of poles is %d but you should provide %d" %
(len(poles), A.shape[0]))
r = np.linalg.matrix_rank(B)
for p in poles:
if sum(p == poles) > r:
raise ValueError("at least one of the requested pole is repeated "
"more than rank(B) times")
# Choose update method
update_loop = _YT_loop
if method not in ('KNV0','YT'):
raise ValueError("The method keyword must be one of 'YT' or 'KNV0'")
if method == "KNV0":
update_loop = _KNV0_loop
if not all(np.isreal(poles)):
raise ValueError("Complex poles are not supported by KNV0")
if maxiter < 1:
raise ValueError("maxiter must be at least equal to 1")
# We do not check rtol <= 0 as the user can use a negative rtol to
# force maxiter iterations
if rtol > 1:
raise ValueError("rtol can not be greater than 1")
return update_loop, poles
def _order_complex_poles(poles):
"""
Check we have complex conjugates pairs and reorder P according to YT, ie
real_poles, complex_i, conjugate complex_i, ....
The lexicographic sort on the complex poles is added to help the user to
compare sets of poles.
"""
ordered_poles = np.sort(poles[np.isreal(poles)])
im_poles = []
for p in np.sort(poles[np.imag(poles) < 0]):
if np.conj(p) in poles:
im_poles.extend((p, np.conj(p)))
ordered_poles = np.hstack((ordered_poles, im_poles))
if poles.shape[0] != len(ordered_poles):
raise ValueError("Complex poles must come with their conjugates")
return ordered_poles
def _KNV0(B, ker_pole, transfer_matrix, j, poles):
"""
Algorithm "KNV0" Kautsky et Al. Robust pole
assignment in linear state feedback, Int journal of Control
1985, vol 41 p 1129->1155
https://la.epfl.ch/files/content/sites/la/files/
users/105941/public/KautskyNicholsDooren
"""
# Remove xj form the base
transfer_matrix_not_j = np.delete(transfer_matrix, j, axis=1)
# If we QR this matrix in full mode Q=Q0|Q1
# then Q1 will be a single column orthogonnal to
# Q0, that's what we are looking for !
# After merge of gh-4249 great speed improvements could be achieved
# using QR updates instead of full QR in the line below
# To debug with numpy qr uncomment the line below
# Q, R = np.linalg.qr(transfer_matrix_not_j, mode="complete")
Q, R = s_qr(transfer_matrix_not_j, mode="full")
mat_ker_pj = np.dot(ker_pole[j], ker_pole[j].T)
yj = np.dot(mat_ker_pj, Q[:, -1])
# If Q[:, -1] is "almost" orthogonal to ker_pole[j] its
# projection into ker_pole[j] will yield a vector
# close to 0. As we are looking for a vector in ker_pole[j]
# simply stick with transfer_matrix[:, j] (unless someone provides me with
# a better choice ?)
if not np.allclose(yj, 0):
xj = yj/np.linalg.norm(yj)
transfer_matrix[:, j] = xj
# KNV does not support complex poles, using YT technique the two lines
# below seem to work 9 out of 10 times but it is not reliable enough:
# transfer_matrix[:, j]=real(xj)
# transfer_matrix[:, j+1]=imag(xj)
# Add this at the beginning of this function if you wish to test
# complex support:
# if ~np.isreal(P[j]) and (j>=B.shape[0]-1 or P[j]!=np.conj(P[j+1])):
# return
# Problems arise when imag(xj)=>0 I have no idea on how to fix this
def _YT_real(ker_pole, Q, transfer_matrix, i, j):
"""
Applies algorithm from YT section 6.1 page 19 related to real pairs
"""
# step 1 page 19
u = Q[:, -2, np.newaxis]
v = Q[:, -1, np.newaxis]
# step 2 page 19
m = np.dot(np.dot(ker_pole[i].T, np.dot(u, v.T) -
np.dot(v, u.T)), ker_pole[j])
# step 3 page 19
um, sm, vm = np.linalg.svd(m)
# mu1, mu2 two first columns of U => 2 first lines of U.T
mu1, mu2 = um.T[:2, :, np.newaxis]
# VM is V.T with numpy we want the first two lines of V.T
nu1, nu2 = vm[:2, :, np.newaxis]
# what follows is a rough python translation of the formulas
# in section 6.2 page 20 (step 4)
transfer_matrix_j_mo_transfer_matrix_j = np.vstack((
transfer_matrix[:, i, np.newaxis],
transfer_matrix[:, j, np.newaxis]))
if not np.allclose(sm[0], sm[1]):
ker_pole_imo_mu1 = np.dot(ker_pole[i], mu1)
ker_pole_i_nu1 = np.dot(ker_pole[j], nu1)
ker_pole_mu_nu = np.vstack((ker_pole_imo_mu1, ker_pole_i_nu1))
else:
ker_pole_ij = np.vstack((
np.hstack((ker_pole[i],
np.zeros(ker_pole[i].shape))),
np.hstack((np.zeros(ker_pole[j].shape),
ker_pole[j]))
))
mu_nu_matrix = np.vstack(
(np.hstack((mu1, mu2)), np.hstack((nu1, nu2)))
)
ker_pole_mu_nu = np.dot(ker_pole_ij, mu_nu_matrix)
transfer_matrix_ij = np.dot(np.dot(ker_pole_mu_nu, ker_pole_mu_nu.T),
transfer_matrix_j_mo_transfer_matrix_j)
if not np.allclose(transfer_matrix_ij, 0):
transfer_matrix_ij = (np.sqrt(2)*transfer_matrix_ij /
np.linalg.norm(transfer_matrix_ij))
transfer_matrix[:, i] = transfer_matrix_ij[
:transfer_matrix[:, i].shape[0], 0
]
transfer_matrix[:, j] = transfer_matrix_ij[
transfer_matrix[:, i].shape[0]:, 0
]
else:
# As in knv0 if transfer_matrix_j_mo_transfer_matrix_j is orthogonal to
# Vect{ker_pole_mu_nu} assign transfer_matrixi/transfer_matrix_j to
# ker_pole_mu_nu and iterate. As we are looking for a vector in
# Vect{Matker_pole_MU_NU} (see section 6.1 page 19) this might help
# (that's a guess, not a claim !)
transfer_matrix[:, i] = ker_pole_mu_nu[
:transfer_matrix[:, i].shape[0], 0
]
transfer_matrix[:, j] = ker_pole_mu_nu[
transfer_matrix[:, i].shape[0]:, 0
]
def _YT_complex(ker_pole, Q, transfer_matrix, i, j):
"""
Applies algorithm from YT section 6.2 page 20 related to complex pairs
"""
# step 1 page 20
ur = np.sqrt(2)*Q[:, -2, np.newaxis]
ui = np.sqrt(2)*Q[:, -1, np.newaxis]
u = ur + 1j*ui
# step 2 page 20
ker_pole_ij = ker_pole[i]
m = np.dot(np.dot(np.conj(ker_pole_ij.T), np.dot(u, np.conj(u).T) -
np.dot(np.conj(u), u.T)), ker_pole_ij)
# step 3 page 20
e_val, e_vec = np.linalg.eig(m)
# sort eigenvalues according to their module
e_val_idx = np.argsort(np.abs(e_val))
mu1 = e_vec[:, e_val_idx[-1], np.newaxis]
mu2 = e_vec[:, e_val_idx[-2], np.newaxis]
# what follows is a rough python translation of the formulas
# in section 6.2 page 20 (step 4)
# remember transfer_matrix_i has been split as
# transfer_matrix[i]=real(transfer_matrix_i) and
# transfer_matrix[j]=imag(transfer_matrix_i)
transfer_matrix_j_mo_transfer_matrix_j = (
transfer_matrix[:, i, np.newaxis] +
1j*transfer_matrix[:, j, np.newaxis]
)
if not np.allclose(np.abs(e_val[e_val_idx[-1]]),
np.abs(e_val[e_val_idx[-2]])):
ker_pole_mu = np.dot(ker_pole_ij, mu1)
else:
mu1_mu2_matrix = np.hstack((mu1, mu2))
ker_pole_mu = np.dot(ker_pole_ij, mu1_mu2_matrix)
transfer_matrix_i_j = np.dot(np.dot(ker_pole_mu, np.conj(ker_pole_mu.T)),
transfer_matrix_j_mo_transfer_matrix_j)
if not np.allclose(transfer_matrix_i_j, 0):
transfer_matrix_i_j = (transfer_matrix_i_j /
np.linalg.norm(transfer_matrix_i_j))
transfer_matrix[:, i] = np.real(transfer_matrix_i_j[:, 0])
transfer_matrix[:, j] = np.imag(transfer_matrix_i_j[:, 0])
else:
# same idea as in YT_real
transfer_matrix[:, i] = np.real(ker_pole_mu[:, 0])
transfer_matrix[:, j] = np.imag(ker_pole_mu[:, 0])
def _YT_loop(ker_pole, transfer_matrix, poles, B, maxiter, rtol):
"""
Algorithm "YT" Tits, Yang. Globally Convergent
Algorithms for Robust Pole Assignment by State Feedback
https://hdl.handle.net/1903/5598
The poles P have to be sorted accordingly to section 6.2 page 20
"""
# The IEEE edition of the YT paper gives useful information on the
# optimal update order for the real poles in order to minimize the number
# of times we have to loop over all poles, see page 1442
nb_real = poles[np.isreal(poles)].shape[0]
# hnb => Half Nb Real
hnb = nb_real // 2
# Stick to the indices in the paper and then remove one to get numpy array
# index it is a bit easier to link the code to the paper this way even if it
# is not very clean. The paper is unclear about what should be done when
# there is only one real pole => use KNV0 on this real pole seem to work
if nb_real > 0:
#update the biggest real pole with the smallest one
update_order = [[nb_real], [1]]
else:
update_order = [[],[]]
r_comp = np.arange(nb_real+1, len(poles)+1, 2)
# step 1.a
r_p = np.arange(1, hnb+nb_real % 2)
update_order[0].extend(2*r_p)
update_order[1].extend(2*r_p+1)
# step 1.b
update_order[0].extend(r_comp)
update_order[1].extend(r_comp+1)
# step 1.c
r_p = np.arange(1, hnb+1)
update_order[0].extend(2*r_p-1)
update_order[1].extend(2*r_p)
# step 1.d
if hnb == 0 and np.isreal(poles[0]):
update_order[0].append(1)
update_order[1].append(1)
update_order[0].extend(r_comp)
update_order[1].extend(r_comp+1)
# step 2.a
r_j = np.arange(2, hnb+nb_real % 2)
for j in r_j:
for i in range(1, hnb+1):
update_order[0].append(i)
update_order[1].append(i+j)
# step 2.b
if hnb == 0 and np.isreal(poles[0]):
update_order[0].append(1)
update_order[1].append(1)
update_order[0].extend(r_comp)
update_order[1].extend(r_comp+1)
# step 2.c
r_j = np.arange(2, hnb+nb_real % 2)
for j in r_j:
for i in range(hnb+1, nb_real+1):
idx_1 = i+j
if idx_1 > nb_real:
idx_1 = i+j-nb_real
update_order[0].append(i)
update_order[1].append(idx_1)
# step 2.d
if hnb == 0 and np.isreal(poles[0]):
update_order[0].append(1)
update_order[1].append(1)
update_order[0].extend(r_comp)
update_order[1].extend(r_comp+1)
# step 3.a
for i in range(1, hnb+1):
update_order[0].append(i)
update_order[1].append(i+hnb)
# step 3.b
if hnb == 0 and np.isreal(poles[0]):
update_order[0].append(1)
update_order[1].append(1)
update_order[0].extend(r_comp)
update_order[1].extend(r_comp+1)
update_order = np.array(update_order).T-1
stop = False
nb_try = 0
while nb_try < maxiter and not stop:
det_transfer_matrixb = np.abs(np.linalg.det(transfer_matrix))
for i, j in update_order:
if i == j:
assert i == 0, "i!=0 for KNV call in YT"
assert np.isreal(poles[i]), "calling KNV on a complex pole"
_KNV0(B, ker_pole, transfer_matrix, i, poles)
else:
transfer_matrix_not_i_j = np.delete(transfer_matrix, (i, j),
axis=1)
# after merge of gh-4249 great speed improvements could be
# achieved using QR updates instead of full QR in the line below
#to debug with numpy qr uncomment the line below
#Q, _ = np.linalg.qr(transfer_matrix_not_i_j, mode="complete")
Q, _ = s_qr(transfer_matrix_not_i_j, mode="full")
if np.isreal(poles[i]):
assert np.isreal(poles[j]), "mixing real and complex " + \
"in YT_real" + str(poles)
_YT_real(ker_pole, Q, transfer_matrix, i, j)
else:
assert ~np.isreal(poles[i]), "mixing real and complex " + \
"in YT_real" + str(poles)
_YT_complex(ker_pole, Q, transfer_matrix, i, j)
det_transfer_matrix = np.max((np.sqrt(np.spacing(1)),
np.abs(np.linalg.det(transfer_matrix))))
cur_rtol = np.abs(
(det_transfer_matrix -
det_transfer_matrixb) /
det_transfer_matrix)
if cur_rtol < rtol and det_transfer_matrix > np.sqrt(np.spacing(1)):
# Convergence test from YT page 21
stop = True
nb_try += 1
return stop, cur_rtol, nb_try
def _KNV0_loop(ker_pole, transfer_matrix, poles, B, maxiter, rtol):
"""
Loop over all poles one by one and apply KNV method 0 algorithm
"""
# This method is useful only because we need to be able to call
# _KNV0 from YT without looping over all poles, otherwise it would
# have been fine to mix _KNV0_loop and _KNV0 in a single function
stop = False
nb_try = 0
while nb_try < maxiter and not stop:
det_transfer_matrixb = np.abs(np.linalg.det(transfer_matrix))
for j in range(B.shape[0]):
_KNV0(B, ker_pole, transfer_matrix, j, poles)
det_transfer_matrix = np.max((np.sqrt(np.spacing(1)),
np.abs(np.linalg.det(transfer_matrix))))
cur_rtol = np.abs((det_transfer_matrix - det_transfer_matrixb) /
det_transfer_matrix)
if cur_rtol < rtol and det_transfer_matrix > np.sqrt(np.spacing(1)):
# Convergence test from YT page 21
stop = True
nb_try += 1
return stop, cur_rtol, nb_try
def place_poles(A, B, poles, method="YT", rtol=1e-3, maxiter=30):
"""
Compute K such that eigenvalues (A - dot(B, K))=poles.
K is the gain matrix such as the plant described by the linear system
``AX+BU`` will have its closed-loop poles, i.e the eigenvalues ``A - B*K``,
as close as possible to those asked for in poles.
SISO, MISO and MIMO systems are supported.
Parameters
----------
A, B : ndarray
State-space representation of linear system ``AX + BU``.
poles : array_like
Desired real poles and/or complex conjugates poles.
Complex poles are only supported with ``method="YT"`` (default).
method: {'YT', 'KNV0'}, optional
Which method to choose to find the gain matrix K. One of:
- 'YT': Yang Tits
- 'KNV0': Kautsky, Nichols, Van Dooren update method 0
See References and Notes for details on the algorithms.
rtol: float, optional
After each iteration the determinant of the eigenvectors of
``A - B*K`` is compared to its previous value, when the relative
error between these two values becomes lower than `rtol` the algorithm
stops. Default is 1e-3.
maxiter: int, optional
Maximum number of iterations to compute the gain matrix.
Default is 30.
Returns
-------
full_state_feedback : Bunch object
full_state_feedback is composed of:
gain_matrix : 1-D ndarray
The closed loop matrix K such as the eigenvalues of ``A-BK``
are as close as possible to the requested poles.
computed_poles : 1-D ndarray
The poles corresponding to ``A-BK`` sorted as first the real
poles in increasing order, then the complex congugates in
lexicographic order.
requested_poles : 1-D ndarray
The poles the algorithm was asked to place sorted as above,
they may differ from what was achieved.
X : 2-D ndarray
The transfer matrix such as ``X * diag(poles) = (A - B*K)*X``
(see Notes)
rtol : float
The relative tolerance achieved on ``det(X)`` (see Notes).
`rtol` will be NaN if it is possible to solve the system
``diag(poles) = (A - B*K)``, or 0 when the optimization
algorithms can't do anything i.e when ``B.shape[1] == 1``.
nb_iter : int
The number of iterations performed before converging.
`nb_iter` will be NaN if it is possible to solve the system
``diag(poles) = (A - B*K)``, or 0 when the optimization
algorithms can't do anything i.e when ``B.shape[1] == 1``.
Notes
-----
The Tits and Yang (YT), [2]_ paper is an update of the original Kautsky et
al. (KNV) paper [1]_. KNV relies on rank-1 updates to find the transfer
matrix X such that ``X * diag(poles) = (A - B*K)*X``, whereas YT uses
rank-2 updates. This yields on average more robust solutions (see [2]_
pp 21-22), furthermore the YT algorithm supports complex poles whereas KNV
does not in its original version. Only update method 0 proposed by KNV has
been implemented here, hence the name ``'KNV0'``.
KNV extended to complex poles is used in Matlab's ``place`` function, YT is
distributed under a non-free licence by Slicot under the name ``robpole``.
It is unclear and undocumented how KNV0 has been extended to complex poles
(Tits and Yang claim on page 14 of their paper that their method can not be
used to extend KNV to complex poles), therefore only YT supports them in
this implementation.
As the solution to the problem of pole placement is not unique for MIMO
systems, both methods start with a tentative transfer matrix which is
altered in various way to increase its determinant. Both methods have been
proven to converge to a stable solution, however depending on the way the
initial transfer matrix is chosen they will converge to different
solutions and therefore there is absolutely no guarantee that using
``'KNV0'`` will yield results similar to Matlab's or any other
implementation of these algorithms.
Using the default method ``'YT'`` should be fine in most cases; ``'KNV0'``
is only provided because it is needed by ``'YT'`` in some specific cases.
Furthermore ``'YT'`` gives on average more robust results than ``'KNV0'``
when ``abs(det(X))`` is used as a robustness indicator.
[2]_ is available as a technical report on the following URL:
https://hdl.handle.net/1903/5598
References
----------
.. [1] J. Kautsky, N.K. Nichols and P. van Dooren, "Robust pole assignment
in linear state feedback", International Journal of Control, Vol. 41
pp. 1129-1155, 1985.
.. [2] A.L. Tits and Y. Yang, "Globally convergent algorithms for robust
pole assignment by state feedback", IEEE Transactions on Automatic
Control, Vol. 41, pp. 1432-1452, 1996.
Examples
--------
A simple example demonstrating real pole placement using both KNV and YT
algorithms. This is example number 1 from section 4 of the reference KNV
publication ([1]_):
>>> import numpy as np
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
>>> A = np.array([[ 1.380, -0.2077, 6.715, -5.676 ],
... [-0.5814, -4.290, 0, 0.6750 ],
... [ 1.067, 4.273, -6.654, 5.893 ],
... [ 0.0480, 4.273, 1.343, -2.104 ]])
>>> B = np.array([[ 0, 5.679 ],
... [ 1.136, 1.136 ],
... [ 0, 0, ],
... [-3.146, 0 ]])
>>> P = np.array([-0.2, -0.5, -5.0566, -8.6659])
Now compute K with KNV method 0, with the default YT method and with the YT
method while forcing 100 iterations of the algorithm and print some results
after each call.
>>> fsf1 = signal.place_poles(A, B, P, method='KNV0')
>>> fsf1.gain_matrix
array([[ 0.20071427, -0.96665799, 0.24066128, -0.10279785],
[ 0.50587268, 0.57779091, 0.51795763, -0.41991442]])
>>> fsf2 = signal.place_poles(A, B, P) # uses YT method
>>> fsf2.computed_poles
array([-8.6659, -5.0566, -0.5 , -0.2 ])
>>> fsf3 = signal.place_poles(A, B, P, rtol=-1, maxiter=100)
>>> fsf3.X
array([[ 0.52072442+0.j, -0.08409372+0.j, -0.56847937+0.j, 0.74823657+0.j],
[-0.04977751+0.j, -0.80872954+0.j, 0.13566234+0.j, -0.29322906+0.j],
[-0.82266932+0.j, -0.19168026+0.j, -0.56348322+0.j, -0.43815060+0.j],
[ 0.22267347+0.j, 0.54967577+0.j, -0.58387806+0.j, -0.40271926+0.j]])
The absolute value of the determinant of X is a good indicator to check the
robustness of the results, both ``'KNV0'`` and ``'YT'`` aim at maximizing
it. Below a comparison of the robustness of the results above:
>>> abs(np.linalg.det(fsf1.X)) < abs(np.linalg.det(fsf2.X))
True
>>> abs(np.linalg.det(fsf2.X)) < abs(np.linalg.det(fsf3.X))
True
Now a simple example for complex poles:
>>> A = np.array([[ 0, 7/3., 0, 0 ],
... [ 0, 0, 0, 7/9. ],
... [ 0, 0, 0, 0 ],
... [ 0, 0, 0, 0 ]])
>>> B = np.array([[ 0, 0 ],
... [ 0, 0 ],
... [ 1, 0 ],
... [ 0, 1 ]])
>>> P = np.array([-3, -1, -2-1j, -2+1j]) / 3.
>>> fsf = signal.place_poles(A, B, P, method='YT')
We can plot the desired and computed poles in the complex plane:
>>> t = np.linspace(0, 2*np.pi, 401)
>>> plt.plot(np.cos(t), np.sin(t), 'k--') # unit circle
>>> plt.plot(fsf.requested_poles.real, fsf.requested_poles.imag,
... 'wo', label='Desired')
>>> plt.plot(fsf.computed_poles.real, fsf.computed_poles.imag, 'bx',
... label='Placed')
>>> plt.grid()
>>> plt.axis('image')
>>> plt.axis([-1.1, 1.1, -1.1, 1.1])
>>> plt.legend(bbox_to_anchor=(1.05, 1), loc=2, numpoints=1)
"""
# Move away all the inputs checking, it only adds noise to the code
update_loop, poles = _valid_inputs(A, B, poles, method, rtol, maxiter)
# The current value of the relative tolerance we achieved
cur_rtol = 0
# The number of iterations needed before converging
nb_iter = 0
# Step A: QR decomposition of B page 1132 KN
# to debug with numpy qr uncomment the line below
# u, z = np.linalg.qr(B, mode="complete")
u, z = s_qr(B, mode="full")
rankB = np.linalg.matrix_rank(B)
u0 = u[:, :rankB]
u1 = u[:, rankB:]
z = z[:rankB, :]
# If we can use the identity matrix as X the solution is obvious
if B.shape[0] == rankB:
# if B is square and full rank there is only one solution
# such as (A+BK)=inv(X)*diag(P)*X with X=eye(A.shape[0])
# i.e K=inv(B)*(diag(P)-A)
# if B has as many lines as its rank (but not square) there are many
# solutions and we can choose one using least squares
# => use lstsq in both cases.
# In both cases the transfer matrix X will be eye(A.shape[0]) and I
# can hardly think of a better one so there is nothing to optimize
#
# for complex poles we use the following trick
#
# |a -b| has for eigenvalues a+b and a-b
# |b a|
#
# |a+bi 0| has the obvious eigenvalues a+bi and a-bi
# |0 a-bi|
#
# e.g solving the first one in R gives the solution
# for the second one in C
diag_poles = np.zeros(A.shape)
idx = 0
while idx < poles.shape[0]:
p = poles[idx]
diag_poles[idx, idx] = np.real(p)
if ~np.isreal(p):
diag_poles[idx, idx+1] = -np.imag(p)
diag_poles[idx+1, idx+1] = np.real(p)
diag_poles[idx+1, idx] = np.imag(p)
idx += 1 # skip next one
idx += 1
gain_matrix = np.linalg.lstsq(B, diag_poles-A, rcond=-1)[0]
transfer_matrix = np.eye(A.shape[0])
cur_rtol = np.nan
nb_iter = np.nan
else:
# step A (p1144 KNV) and beginning of step F: decompose
# dot(U1.T, A-P[i]*I).T and build our set of transfer_matrix vectors
# in the same loop
ker_pole = []
# flag to skip the conjugate of a complex pole
skip_conjugate = False
# select orthonormal base ker_pole for each Pole and vectors for
# transfer_matrix
for j in range(B.shape[0]):
if skip_conjugate:
skip_conjugate = False
continue
pole_space_j = np.dot(u1.T, A-poles[j]*np.eye(B.shape[0])).T
# after QR Q=Q0|Q1
# only Q0 is used to reconstruct the qr'ed (dot Q, R) matrix.
# Q1 is orthogonnal to Q0 and will be multiplied by the zeros in
# R when using mode "complete". In default mode Q1 and the zeros
# in R are not computed
# To debug with numpy qr uncomment the line below
# Q, _ = np.linalg.qr(pole_space_j, mode="complete")
Q, _ = s_qr(pole_space_j, mode="full")
ker_pole_j = Q[:, pole_space_j.shape[1]:]
# We want to select one vector in ker_pole_j to build the transfer
# matrix, however qr returns sometimes vectors with zeros on the
# same line for each pole and this yields very long convergence
# times.
# Or some other times a set of vectors, one with zero imaginary
# part and one (or several) with imaginary parts. After trying
# many ways to select the best possible one (eg ditch vectors
# with zero imaginary part for complex poles) I ended up summing
# all vectors in ker_pole_j, this solves 100% of the problems and
# is a valid choice for transfer_matrix.
# This way for complex poles we are sure to have a non zero
# imaginary part that way, and the problem of lines full of zeros
# in transfer_matrix is solved too as when a vector from
# ker_pole_j has a zero the other one(s) when
# ker_pole_j.shape[1]>1) for sure won't have a zero there.
transfer_matrix_j = np.sum(ker_pole_j, axis=1)[:, np.newaxis]
transfer_matrix_j = (transfer_matrix_j /
np.linalg.norm(transfer_matrix_j))
if ~np.isreal(poles[j]): # complex pole
transfer_matrix_j = np.hstack([np.real(transfer_matrix_j),
np.imag(transfer_matrix_j)])
ker_pole.extend([ker_pole_j, ker_pole_j])
# Skip next pole as it is the conjugate
skip_conjugate = True
else: # real pole, nothing to do
ker_pole.append(ker_pole_j)
if j == 0:
transfer_matrix = transfer_matrix_j
else:
transfer_matrix = np.hstack((transfer_matrix, transfer_matrix_j))
if rankB > 1: # otherwise there is nothing we can optimize
stop, cur_rtol, nb_iter = update_loop(ker_pole, transfer_matrix,
poles, B, maxiter, rtol)
if not stop and rtol > 0:
# if rtol<=0 the user has probably done that on purpose,
# don't annoy him
err_msg = (
"Convergence was not reached after maxiter iterations.\n"
f"You asked for a tolerance of {rtol}, we got {cur_rtol}."
)
warnings.warn(err_msg, stacklevel=2)
# reconstruct transfer_matrix to match complex conjugate pairs,
# ie transfer_matrix_j/transfer_matrix_j+1 are
# Re(Complex_pole), Im(Complex_pole) now and will be Re-Im/Re+Im after
transfer_matrix = transfer_matrix.astype(complex)
idx = 0
while idx < poles.shape[0]-1:
if ~np.isreal(poles[idx]):
rel = transfer_matrix[:, idx].copy()
img = transfer_matrix[:, idx+1]
# rel will be an array referencing a column of transfer_matrix
# if we don't copy() it will changer after the next line and
# and the line after will not yield the correct value
transfer_matrix[:, idx] = rel-1j*img
transfer_matrix[:, idx+1] = rel+1j*img
idx += 1 # skip next one
idx += 1
try:
m = np.linalg.solve(transfer_matrix.T, np.dot(np.diag(poles),
transfer_matrix.T)).T
gain_matrix = np.linalg.solve(z, np.dot(u0.T, m-A))
except np.linalg.LinAlgError as e:
raise ValueError("The poles you've chosen can't be placed. "
"Check the controllability matrix and try "
"another set of poles") from e
# Beware: Kautsky solves A+BK but the usual form is A-BK
gain_matrix = -gain_matrix
# K still contains complex with ~=0j imaginary parts, get rid of them
gain_matrix = np.real(gain_matrix)
full_state_feedback = Bunch()
full_state_feedback.gain_matrix = gain_matrix
full_state_feedback.computed_poles = _order_complex_poles(
np.linalg.eig(A - np.dot(B, gain_matrix))[0]
)
full_state_feedback.requested_poles = poles
full_state_feedback.X = transfer_matrix
full_state_feedback.rtol = cur_rtol
full_state_feedback.nb_iter = nb_iter
return full_state_feedback
def dlsim(system, u, t=None, x0=None):
"""
Simulate output of a discrete-time linear system.
Parameters
----------
system : tuple of array_like or instance of `dlti`
A tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1: (instance of `dlti`)
* 3: (num, den, dt)
* 4: (zeros, poles, gain, dt)
* 5: (A, B, C, D, dt)
u : array_like
An input array describing the input at each time `t` (interpolation is
assumed between given times). If there are multiple inputs, then each
column of the rank-2 array represents an input.
t : array_like, optional
The time steps at which the input is defined. If `t` is given, it
must be the same length as `u`, and the final value in `t` determines
the number of steps returned in the output.
x0 : array_like, optional
The initial conditions on the state vector (zero by default).
Returns
-------
tout : ndarray
Time values for the output, as a 1-D array.
yout : ndarray
System response, as a 1-D array.
xout : ndarray, optional
Time-evolution of the state-vector. Only generated if the input is a
`StateSpace` system.
See Also
--------
lsim, dstep, dimpulse, cont2discrete
Examples
--------
A simple integrator transfer function with a discrete time step of 1.0
could be implemented as:
>>> import numpy as np
>>> from scipy import signal
>>> tf = ([1.0,], [1.0, -1.0], 1.0)
>>> t_in = [0.0, 1.0, 2.0, 3.0]
>>> u = np.asarray([0.0, 0.0, 1.0, 1.0])
>>> t_out, y = signal.dlsim(tf, u, t=t_in)
>>> y.T
array([[ 0., 0., 0., 1.]])
"""
# Convert system to dlti-StateSpace
if isinstance(system, lti):
raise AttributeError('dlsim can only be used with discrete-time dlti '
'systems.')
elif not isinstance(system, dlti):
system = dlti(*system[:-1], dt=system[-1])
# Condition needed to ensure output remains compatible
is_ss_input = isinstance(system, StateSpace)
system = system._as_ss()
u = np.atleast_1d(u)
if u.ndim == 1:
u = np.atleast_2d(u).T
if t is None:
out_samples = len(u)
stoptime = (out_samples - 1) * system.dt
else:
stoptime = t[-1]
out_samples = int(np.floor(stoptime / system.dt)) + 1
# Pre-build output arrays
xout = np.zeros((out_samples, system.A.shape[0]))
yout = np.zeros((out_samples, system.C.shape[0]))
tout = np.linspace(0.0, stoptime, num=out_samples)
# Check initial condition
if x0 is None:
xout[0, :] = np.zeros((system.A.shape[1],))
else:
xout[0, :] = np.asarray(x0)
# Pre-interpolate inputs into the desired time steps
if t is None:
u_dt = u
else:
if len(u.shape) == 1:
u = u[:, np.newaxis]
u_dt = make_interp_spline(t, u, k=1)(tout)
# Simulate the system
for i in range(0, out_samples - 1):
xout[i+1, :] = (np.dot(system.A, xout[i, :]) +
np.dot(system.B, u_dt[i, :]))
yout[i, :] = (np.dot(system.C, xout[i, :]) +
np.dot(system.D, u_dt[i, :]))
# Last point
yout[out_samples-1, :] = (np.dot(system.C, xout[out_samples-1, :]) +
np.dot(system.D, u_dt[out_samples-1, :]))
if is_ss_input:
return tout, yout, xout
else:
return tout, yout
def dimpulse(system, x0=None, t=None, n=None):
"""
Impulse response of discrete-time system.
Parameters
----------
system : tuple of array_like or instance of `dlti`
A tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1: (instance of `dlti`)
* 3: (num, den, dt)
* 4: (zeros, poles, gain, dt)
* 5: (A, B, C, D, dt)
x0 : array_like, optional
Initial state-vector. Defaults to zero.
t : array_like, optional
Time points. Computed if not given.
n : int, optional
The number of time points to compute (if `t` is not given).
Returns
-------
tout : ndarray
Time values for the output, as a 1-D array.
yout : tuple of ndarray
Impulse response of system. Each element of the tuple represents
the output of the system based on an impulse in each input.
See Also
--------
impulse, dstep, dlsim, cont2discrete
Examples
--------
>>> import numpy as np
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
>>> butter = signal.dlti(*signal.butter(3, 0.5))
>>> t, y = signal.dimpulse(butter, n=25)
>>> plt.step(t, np.squeeze(y))
>>> plt.grid()
>>> plt.xlabel('n [samples]')
>>> plt.ylabel('Amplitude')
"""
# Convert system to dlti-StateSpace
if isinstance(system, dlti):
system = system._as_ss()
elif isinstance(system, lti):
raise AttributeError('dimpulse can only be used with discrete-time '
'dlti systems.')
else:
system = dlti(*system[:-1], dt=system[-1])._as_ss()
# Default to 100 samples if unspecified
if n is None:
n = 100
# If time is not specified, use the number of samples
# and system dt
if t is None:
t = np.linspace(0, n * system.dt, n, endpoint=False)
else:
t = np.asarray(t)
# For each input, implement a step change
yout = None
for i in range(0, system.inputs):
u = np.zeros((t.shape[0], system.inputs))
u[0, i] = 1.0
one_output = dlsim(system, u, t=t, x0=x0)
if yout is None:
yout = (one_output[1],)
else:
yout = yout + (one_output[1],)
tout = one_output[0]
return tout, yout
def dstep(system, x0=None, t=None, n=None):
"""
Step response of discrete-time system.
Parameters
----------
system : tuple of array_like
A tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1: (instance of `dlti`)
* 3: (num, den, dt)
* 4: (zeros, poles, gain, dt)
* 5: (A, B, C, D, dt)
x0 : array_like, optional
Initial state-vector. Defaults to zero.
t : array_like, optional
Time points. Computed if not given.
n : int, optional
The number of time points to compute (if `t` is not given).
Returns
-------
tout : ndarray
Output time points, as a 1-D array.
yout : tuple of ndarray
Step response of system. Each element of the tuple represents
the output of the system based on a step response to each input.
See Also
--------
step, dimpulse, dlsim, cont2discrete
Examples
--------
>>> import numpy as np
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
>>> butter = signal.dlti(*signal.butter(3, 0.5))
>>> t, y = signal.dstep(butter, n=25)
>>> plt.step(t, np.squeeze(y))
>>> plt.grid()
>>> plt.xlabel('n [samples]')
>>> plt.ylabel('Amplitude')
"""
# Convert system to dlti-StateSpace
if isinstance(system, dlti):
system = system._as_ss()
elif isinstance(system, lti):
raise AttributeError('dstep can only be used with discrete-time dlti '
'systems.')
else:
system = dlti(*system[:-1], dt=system[-1])._as_ss()
# Default to 100 samples if unspecified
if n is None:
n = 100
# If time is not specified, use the number of samples
# and system dt
if t is None:
t = np.linspace(0, n * system.dt, n, endpoint=False)
else:
t = np.asarray(t)
# For each input, implement a step change
yout = None
for i in range(0, system.inputs):
u = np.zeros((t.shape[0], system.inputs))
u[:, i] = np.ones((t.shape[0],))
one_output = dlsim(system, u, t=t, x0=x0)
if yout is None:
yout = (one_output[1],)
else:
yout = yout + (one_output[1],)
tout = one_output[0]
return tout, yout
def dfreqresp(system, w=None, n=10000, whole=False):
r"""
Calculate the frequency response of a discrete-time system.
Parameters
----------
system : an instance of the `dlti` class or a tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1 (instance of `dlti`)
* 2 (numerator, denominator, dt)
* 3 (zeros, poles, gain, dt)
* 4 (A, B, C, D, dt)
w : array_like, optional
Array of frequencies (in radians/sample). Magnitude and phase data is
calculated for every value in this array. If not given a reasonable
set will be calculated.
n : int, optional
Number of frequency points to compute if `w` is not given. The `n`
frequencies are logarithmically spaced in an interval chosen to
include the influence of the poles and zeros of the system.
whole : bool, optional
Normally, if 'w' is not given, frequencies are computed from 0 to the
Nyquist frequency, pi radians/sample (upper-half of unit-circle). If
`whole` is True, compute frequencies from 0 to 2*pi radians/sample.
Returns
-------
w : 1D ndarray
Frequency array [radians/sample]
H : 1D ndarray
Array of complex magnitude values
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``z^2 + 3z + 5`` would be represented as ``[1, 3, 5]``).
.. versionadded:: 0.18.0
Examples
--------
Generating the Nyquist plot of a transfer function
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
Construct the transfer function
:math:`H(z) = \frac{1}{z^2 + 2z + 3}` with a sampling time of 0.05
seconds:
>>> sys = signal.TransferFunction([1], [1, 2, 3], dt=0.05)
>>> w, H = signal.dfreqresp(sys)
>>> plt.figure()
>>> plt.plot(H.real, H.imag, "b")
>>> plt.plot(H.real, -H.imag, "r")
>>> plt.show()
"""
if not isinstance(system, dlti):
if isinstance(system, lti):
raise AttributeError('dfreqresp can only be used with '
'discrete-time systems.')
system = dlti(*system[:-1], dt=system[-1])
if isinstance(system, StateSpace):
# No SS->ZPK code exists right now, just SS->TF->ZPK
system = system._as_tf()
if not isinstance(system, (TransferFunction, ZerosPolesGain)):
raise ValueError('Unknown system type')
if system.inputs != 1 or system.outputs != 1:
raise ValueError("dfreqresp requires a SISO (single input, single "
"output) system.")
if w is not None:
worN = w
else:
worN = n
if isinstance(system, TransferFunction):
# Convert numerator and denominator from polynomials in the variable
# 'z' to polynomials in the variable 'z^-1', as freqz expects.
num, den = TransferFunction._z_to_zinv(system.num.ravel(), system.den)
w, h = freqz(num, den, worN=worN, whole=whole)
elif isinstance(system, ZerosPolesGain):
w, h = freqz_zpk(system.zeros, system.poles, system.gain, worN=worN,
whole=whole)
return w, h
def dbode(system, w=None, n=100):
r"""
Calculate Bode magnitude and phase data of a discrete-time system.
Parameters
----------
system : an instance of the LTI class or a tuple describing the system.
The following gives the number of elements in the tuple and
the interpretation:
* 1 (instance of `dlti`)
* 2 (num, den, dt)
* 3 (zeros, poles, gain, dt)
* 4 (A, B, C, D, dt)
w : array_like, optional
Array of frequencies (in radians/sample). Magnitude and phase data is
calculated for every value in this array. If not given a reasonable
set will be calculated.
n : int, optional
Number of frequency points to compute if `w` is not given. The `n`
frequencies are logarithmically spaced in an interval chosen to
include the influence of the poles and zeros of the system.
Returns
-------
w : 1D ndarray
Frequency array [rad/time_unit]
mag : 1D ndarray
Magnitude array [dB]
phase : 1D ndarray
Phase array [deg]
Notes
-----
If (num, den) is passed in for ``system``, coefficients for both the
numerator and denominator should be specified in descending exponent
order (e.g. ``z^2 + 3z + 5`` would be represented as ``[1, 3, 5]``).
.. versionadded:: 0.18.0
Examples
--------
>>> from scipy import signal
>>> import matplotlib.pyplot as plt
Construct the transfer function :math:`H(z) = \frac{1}{z^2 + 2z + 3}` with
a sampling time of 0.05 seconds:
>>> sys = signal.TransferFunction([1], [1, 2, 3], dt=0.05)
Equivalent: sys.bode()
>>> w, mag, phase = signal.dbode(sys)
>>> plt.figure()
>>> plt.semilogx(w, mag) # Bode magnitude plot
>>> plt.figure()
>>> plt.semilogx(w, phase) # Bode phase plot
>>> plt.show()
"""
w, y = dfreqresp(system, w=w, n=n)
if isinstance(system, dlti):
dt = system.dt
else:
dt = system[-1]
mag = 20.0 * numpy.log10(abs(y))
phase = numpy.rad2deg(numpy.unwrap(numpy.angle(y)))
return w / dt, mag, phase
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